JP2006230075A - Switching regulator connection - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a switching power circuit capable of restraining loss of a transformer itself. <P>SOLUTION: Between a rectification circuit 59 and a smoothing circuit 63, there is provided a capacitor 2 of which capacity is larger than that of a capacitor 57 as a parasitic element of a diode 58. <P>COPYRIGHT: (C)2006,JPO&NCIPI

Description

  The present invention relates to a switching power supply circuit that converts DC power to AC power by a conversion circuit composed of a plurality of switching elements, converts the DC power again to DC power by a rectifier circuit and a smoothing circuit via a transformer, and outputs the DC power.

  Conventionally, as a switching power supply circuit that soft-switches a switching element of a conversion circuit that converts DC power into AC power, for example, there is a switching power supply circuit that changes a pulse width of a driving signal of the switching element (for example, Patent Document 1). reference).

  In addition, as a switching power supply circuit that soft-switches the switching element of the conversion circuit, for example, in the full-bridge conversion circuit, the phase of the driving signal of the switching element of one bridge is changed to the driving signal of the switching element of the other bridge There is also a so-called phase shift type switching power supply circuit that shifts with respect to the phase (see, for example, Patent Document 2). These switching power supply circuits can be easily configured because there is almost no increase in the number of components.

  Further, as a switching power supply circuit for soft-switching the switching element of the conversion circuit, for example, a capacitor connected in parallel to each of the switching elements of the conversion circuit, a leakage inductor provided between the conversion circuit and the transformer, There is also a so-called zero-volt switching type (hereinafter referred to as ZVS type) switching power supply circuit that turns on and off the switching element while preventing voltage from being applied to both ends of the switching element due to resonance of the resonance circuit constituted by Reference 3).

FIG. 5 is a diagram illustrating an existing ZVS switching power supply circuit.
The switching power supply circuit 50 shown in FIG. 5 includes four switching elements 52 (52-1 to 52-4) to which capacitors 51 (51-1 to 51-4) are connected in parallel, respectively. A conversion circuit 54 that converts DC power into AC power, a transformer 55 that boosts or steps down AC power output from the conversion circuit 54, a leakage inductor 56 provided between the conversion circuit 54 and the transformer 55, and a capacitor 57 A rectifier circuit 59 configured to rectify AC power output from the transformer 55, which includes four diodes 58 (58-1 to 58-4) connected in parallel to each other (57-1 to 57-4), and an inductor 60 And a capacitor 61, and a smoothing circuit 63 that smoothes the output from the rectifier circuit 59 and outputs it to the load 62. To have.

  A capacitor 64 provided between the DC power supply 53 and the conversion circuit 54 smoothes the DC power from the DC power supply 53 and accumulates the output regenerated from the conversion circuit 54. Capacitors 51-1 to 51-4 may be constituted by parasitic elements of switching elements 52-1 to 52-4, or capacitors are externally attached to switching elements 52-1 to 52-4, respectively. You may comprise by. Capacitors 57-1 to 57-4 are constituted by parasitic elements of diodes 58-1 to 58-4. The leakage inductor 56 may be configured inside the transformer 55 together with the primary side coil or the secondary side coil of the transformer 55, or may be configured outside the transformer 55.

  In the conversion circuit 54, switching elements 52-1 and 52-2, which are MOSFETs (Metal Oxide Semiconductor Field Effect Transistors), are bridge-connected, and the middle point thereof is a plus terminal of a primary side coil of a transformer 55 via a leakage inductor 56. The switching elements 52-3 and 52-4, which are MOSFETs, are bridge-connected, and the midpoint thereof is connected to the negative terminal of the primary side coil of the transformer 55.

Next, the operation of the conversion circuit 54 will be described.
FIG. 6A is a diagram schematically showing a circuit on the primary side of the transformer 55 in the switching power supply circuit 50. In addition, the same code | symbol is attached | subjected to the same structure as the structure shown in FIG.

  As shown in FIG. 6A, in the conversion circuit 54, a bridge constituted by the switching elements 52-1 and 52-2 is referred to as an “advanced phase bridge”, and is constituted by the switching elements 52-3 and 52-4. The bridge is called “lagging phase bridge”.

  FIG. 6B is a diagram showing drive signals input to the “leading phase bridge” and the “lagging phase bridge”, respectively. In FIG. 6B, the drive signal input to the “leading phase bridge” switching element 52-1 is referred to as “leading phase PWM (Pulse Width Modulation) signal”, and the switching element 52 − of “lagging phase bridge” is used. The drive signal input to 4 is referred to as “delayed phase PWM signal”.

  The “leading phase PWM signal” and the “lagging phase PWM signal” shown in FIG. 6B have the same frequency and the same ON width, and the “lagging phase PWM signal” with respect to the phase of the “leading phase PWM signal”. The phase of the “delayed phase PWM signal” is phase-shifted with respect to the “leading phase PWM signal”.

  For example, when the phase of the “lagging phase PWM signal” is shifted so as to advance with respect to the phase of the “leading phase PWM signal”, as shown in FIG. And the period during which the “delayed phase PWM signal” is turned on, that is, the period during which the voltage is applied to the primary coil 55-1 of the transformer 55 shown in FIG.

  On the other hand, when the phase of the “delayed phase PWM signal” is phase-shifted so as to be delayed with respect to the phase of the “advanced phase PWM signal”, the period during which the voltage is applied to the primary side coil 55-1 of the transformer 55 is gradually increased. It will become shorter.

  FIG. 7 is a diagram showing a current flow when the switching elements 52-1 to 52-4 are driven. In addition, the same code | symbol is attached | subjected to the same structure as the structure shown to Fig.6 (a). Moreover, the arrows shown in FIGS. 7A to 7F indicate the flow of current.

  8 shows drive signals S1 to S4 input to the switching elements 52-1 to 52-4, the leakage inductor 56, the current Ip flowing through the primary coil 55-1 of the transformer 55, and the leakage inductor 56, respectively. 4 is a diagram illustrating a voltage VAB applied to the primary side coil 55-1 of the transformer 55. FIG. The switching elements 52-1 and 52-2 receive drive signals S1 and S2 that are alternately turned on and off with a predetermined dead time. The switching elements 52-3 and 52-4 receive drive signals S3 and S4 that are alternately turned on and off with a predetermined dead time.

  First, in a period (period (1) shown in FIG. 8) in which the switching elements 52-1 and 52-4 are on and the other switching elements 52 are off, as shown in FIG. 8, the leakage inductor 56 and the transformer 55 A positive voltage of the power supply voltage of the DC power supply 53 is applied to the primary coil 55-1 (A-B section shown in FIG. 7). Moreover, in this period (1), as shown to Fig.7 (a), a positive electric current flows into an AB section. Thereby, the conversion circuit 54 can supply AC power to the transformer 55 in the period (1).

  Next, in the period (period (2) shown in FIG. 8) in which the switching element 52-4 is turned on and the other switching elements 52 are turned off, as shown in FIG. It gradually decreases until the voltage reaches zero. That is, in this period (2), as shown in FIG. 7B, the capacitor 51-1 is charged and discharged until the charge charged in the capacitor 51-2 becomes zero. The capacitors 51-1 and 51-2 and the leakage inductor 56 constitute a resonance circuit. Since the capacitors 51-1 and 51-2 have capacities, the voltage between the drain and the source of the switching element 52-1 gradually increases, so that the loss of the switching element 52-1 can be reduced.

  Next, in a period (period (3) shown in FIG. 8) in which the switching elements 52-2 and 52-4 are turned on and the other switching elements 52 are turned off, as shown in FIG. When the voltage across the switching element 52-1 becomes the power supply voltage of the DC power supply 53 due to the charging of −1, the diode connected in parallel to the switching element 52-2 becomes conductive. Therefore, in this period (3), the switching element 52-2 is turned on while the drain-source voltage of the switching element 52-2 is maintained at zero.

  Next, in a period (period (4) shown in FIG. 8) in which the switching element 52-2 is turned on and the other switching elements 52 are turned off, as shown in FIG. The voltage gradually decreases until the voltage becomes a negative voltage of the power supply voltage of the DC power supply 53. That is, in this period (4), as shown in FIG. 7 (d), the capacitor 51-4 is charged and discharged until the charge charged in the capacitor 51-3 becomes zero. The capacitor 51-3, the capacitor 51-4, and the leakage inductor 56 constitute a resonance circuit. Since the capacitors 51-3 and 51-4 have a capacity, the voltage between the drain and source of the switching element 52-4 gradually increases, so that the loss of the switching element 52-4 can be reduced.

  Next, in a period (period (5) shown in FIG. 8) in which the switching elements 52-2 and 52-3 are turned on and the other switching elements 52 are turned off, as shown in FIG. When the voltage across the switching element 52-4 becomes the power supply voltage of the DC power supply 53 due to the charging of -4, the diode connected in parallel to the switching element 52-3 becomes conductive. Therefore, in this period (5), the switching element 52-3 is turned on while the drain-source voltage of the switching element 52-3 is maintained at zero.

  Further, in a period (period (6) shown in FIG. 8) in which the switching elements 52-2 and 52-3 are turned on and the other switching elements 52 are turned off, as shown in FIG. A negative voltage of the power supply voltage of the DC power supply 53 is applied to the power supply. Further, during this period (6), as shown in FIG. 7 (f), AC power is regenerated in the circuit on the primary side of the transformer 55, and is negatively applied to the leakage inductor 56 and the primary side coil 55-1 of the transformer 55. Current flows. Thereby, the conversion circuit 54 can supply AC power to the transformer 55 in the period (6).

As described above, in the switching power supply circuit 50, during the periods (2) to (5), the resonance circuit constituted by the capacitors 51-1 to 51-4 and the leakage inductor 56 resonates at the time of turn-off and is applied to both ends of the switching element 52. The voltage increases gradually. Alternatively, at the time of turn-on, the diode 51 of the switching element 52 is turned on by returning the energy stored in the leakage inductor 56 during the period (1) (or period (6)). Thereby, each switching loss of switching element 52-1-52-4 can be reduced.
Japanese Patent Laid-Open No. 10-337021 (pages 3 to 10 and FIGS. 1 to 5) USP 4864479 (columns 3-16, FIGS. 1-7) Republication No. 01-071896 (Pages 5-29, Figures 1-24)

  However, in the switching power supply circuit 50, due to the voltage drop caused by the leakage inductor 56, the rising of the current Ip flowing through the primary side coil 55-1 of the transformer 55 becomes gentle as shown in FIG. Therefore, the switching power supply circuit 50 does not perform phase shift, and the secondary side of the transformer 55 when the duty of the drive signal of the switching element 52 is equal as compared with the hard switching system that does not include the capacitor 51 and the leakage inductor 56. The AC power that can be transmitted to the coil is reduced.

  That is, in the switching power supply circuit 50, the current Ip flowing through the primary side coil 55-1 of the transformer 55 is equal to the primary side coil of the transformer 55, as compared with the hard switching type switching power supply circuit. The time product of the current Ip flowing in the primary side coil 55-1 of the transformer 55 and the voltage VAB applied to the primary side coil 55-1 which is delayed with respect to the voltage VAB applied to the 55-1 is reduced, The AC power transmitted to the secondary coil of the transformer 55 is reduced.

  In the switching power supply circuit 50, when the switching elements 52 are to be zero-volt switched for a long period of time, it is necessary to increase the inductance of the leakage inductor 56. As described above, when the inductance of the leakage inductor 56 is increased, the circulating current (reactive power) of the circuit on the primary side of the transformer 55 is increased, and there is a problem that the AC power transmitted to the secondary coil of the transformer 55 is reduced. .

  Therefore, the switching power supply circuit 50 has a higher output than the hard switching switching power supply circuit when compared with the hard switching switching power supply circuit when each switching element 52 is to be zero-volt switched for a long period of time. There is a problem that the winding ratio of the transformer 55 needs to be increased, and the loss of the transformer 55 increases.

  Therefore, for example, the switching power supply circuit 50 can reduce the switching loss of the switching element 52 as compared with the hard switching type switching power supply circuit by increasing the frequency of the drive signal of the switching element 52. The copper loss of the transformer 55 increases due to an increase in AC resistance due to the skin effect and an increase in the winding ratio of the transformer 55.

  Therefore, an object of the present invention is to provide a switching power supply circuit capable of suppressing the loss of the transformer itself.

In order to solve the above problems, the present invention adopts the following configuration.
That is, the switching power supply circuit according to the present invention includes first, second, third, and fourth switching elements each having a first capacitor connected in parallel, and the first switching element and the second switching element. Switching elements are connected in series so that the first switching element is on the high potential side to form a first phase bridge, and the third switching element and the fourth switching element are the third switching element. The elements are connected in series so as to be on the high potential side to form a second phase bridge, the first and second switching elements are alternately turned on and off, and the third and fourth switching elements are A converter circuit that converts DC power into AC power by alternately turning on and off, an inductor that constitutes a resonance circuit with the first capacitor, and an inductor A transformer for stepping up or stepping down the AC power output from the converter circuit, a rectifier circuit configured by a diode for rectifying the AC power output from the transformer, and a smoothing circuit for smoothing the output from the rectifier circuit. And the phase of the drive signal input to the first phase bridge is shifted with respect to the phase of the drive signal input to the second phase bridge, and the switching elements are set to zero volts by resonance of the resonance circuit. A switching power supply circuit for switching, wherein a second capacitor is provided between the rectifier circuit and the smoothing circuit.

  Thus, by providing the second capacitor between the rectifier circuit and the smoothing circuit, the current flowing through the transformer can be advanced with respect to the voltage applied to the transformer. Thereby, since the time product of the voltage applied to the transformer and the current flowing through the transformer can be increased, the AC power supplied to the transformer can be increased. Therefore, since the winding ratio of the transformer can be reduced, the efficiency of the transformer itself can be improved.

The capacitance of the second capacitor of the switching power supply circuit may be set to be larger than the capacitance of a third capacitor that is a parasitic element of the diode.
In this way, by making the capacitance of the second capacitor larger than the capacitance of the third capacitor, which is a parasitic element of the diode, the oscillation of the current due to the resonance of the resonance circuit composed of the inductor and the third conductor is reduced. Since it can be suppressed (that is, the Q value of the resonance circuit constituted by the inductor and the second and third capacitors can be reduced), the peak value of the voltage applied to the diode can be lowered. . As a result, the withstand voltage of the diode can be lowered, so that an inexpensive diode can be used correspondingly, and the cost of the entire switching power supply circuit can be reduced. In addition, since the withstand voltage of the diode can be reduced, a smaller diode can be used, and the circuit scale of the entire switching power supply circuit can be reduced. Furthermore, if a diode with a low withstand voltage is used, the conduction loss is reduced and the efficiency can be improved.

  Further, the capacitance of the second capacitor of the switching power supply circuit is for generating a drive signal for turning on and off each switching element by a resonance frequency of a resonance circuit composed of the inductor and the second capacitor. You may set so that it may become larger than the frequency of a reference signal.

  Further, the capacitance of the second capacitor of the switching power supply circuit may be varied in accordance with fluctuations in DC power input to the conversion circuit or fluctuations in DC power required by a load provided at the subsequent stage of the smoothing circuit. You may comprise.

As a result, the efficiency of the transformer itself can be maintained even if the DC power input to the conversion circuit or the DC power required by the load connected to the subsequent stage of the smoothing circuit fluctuates.
In the switching power supply circuit, the second capacitor includes a plurality of capacitors connected in parallel to each other, and further, a switch that selects a capacitor to be used from among the plurality of capacitors, and the conversion circuit. A control circuit that operates the switch in accordance with fluctuations in DC power or fluctuations in DC power required by a load provided at a subsequent stage of the smoothing circuit may be provided.

  Even with this configuration, the efficiency of the transformer itself can be maintained even if the DC power input to the conversion circuit or the DC power required by the load connected to the subsequent stage of the smoothing circuit fluctuates.

  According to the present invention, the efficiency of the transformer itself can be improved.

Hereinafter, embodiments of the present invention will be described with reference to the drawings.
FIG. 1 is a diagram showing a switching power supply circuit according to an embodiment of the present invention. In addition, the same code | symbol is attached | subjected to the same structure as the structure shown in FIG.

  The switching power supply circuit 1 shown in FIG. 1 includes four switching elements 52 (52-1: first switching element, 52-2: second switching element) to which capacitors 51 (first capacitors) are respectively connected in parallel. , 52-3: third switching element, 52-4: fourth switching element), transformer 55, leakage inductor 56 (inductor), rectifier circuit 59, and smoothing circuit 63. And a capacitor 2 (second capacitor). The transformer 55 may be a step-up type or a step-down type.

  The switching power supply circuit 1 shown in FIG. 1 is characterized in that the capacitor 2 is provided between the rectifier circuit 59 and the smoothing circuit 63. That is, one end of the capacitor 2 is connected to the cathode of the diode 58-3 and one end of the inductor 60, and the other end of the capacitor 2 is connected to the anode of the diode 58-4 and the negative terminal of the capacitor 61.

  FIG. 2A illustrates the drive signals S1 to S4 input to the switching elements 52-1 to 52-4, the leakage inductor 56, and the primary coil 55-1 of the transformer 55 in the switching power supply circuit 1 (FIG. 7). It is a figure which shows the voltage IAB applied to the electric current Ip which flows into AB area | region shown in (4), and AB area | region. Note that the operations of the switching elements 52-1 to 52-4 in the periods (I) to (VI) shown in FIG. 2A are the same as those of the switching elements 52- in the periods (1) to (6) shown in FIG. Since the operations are the same as those of 1 to 52-4, the description of the operations of the switching elements 52-1 to 52-4 in the switching power supply circuit 1 is omitted.

  In the switching power supply circuit 1, current is generated by the leakage inductor 56 and the capacitor 57 (third capacitor) which is a parasitic element of the capacitor 2 and the diode 58 in the period (I) or period (VI) shown in FIG. Ip resonates.

Therefore, the current Ip shown in FIG. 2A is different from the current Ip shown in FIG.
FIG. 2B is a diagram showing the current Ip shown in FIG. 2A and the current Ip shown in FIG. 8 on the same time axis. In FIG. 2B, a current Ip indicated by a solid line indicates the current Ip shown in FIG. 2A, and a current Ip indicated by a broken line indicates the current Ip shown in FIG.

  Compared with the switching power supply circuit 50 shown in FIG. 5, the switching power supply circuit 1 adds a current 2 to the primary coil of the transformer 55. The phase can be advanced. That is, as shown in FIG. 2B, the switching power supply circuit 1 can flow a sharply rising current Ip to the primary coil of the transformer 55 by the leakage inductor 56, the capacitor 2, and the capacitor 57. In the period T shown in FIG. 2B, the time product of the current Ip flowing through the primary side coil of the transformer 55 and the voltage VAB applied to the primary side coil of the transformer 55 is increased more than that of the switching power supply circuit 50. Can do.

  Thereby, the switching power supply circuit 1 can transmit larger AC power to the primary side coil of the transformer 55 than the switching power supply circuit 50 when the duty of the drive signal of the switching power supply circuit 50 and the switching element 52 is the same. Therefore, the winding ratio of the transformer 55 can be reduced, and the efficiency of the transformer 55 itself can be improved.

Further, since there is no need to change the operation control of the switching power supply circuit 1, existing ICs and control methods can be used, and the efficiency of the transformer 55 itself can be easily improved.
In the case of adopting the step-up transformer 55 (the number of turns of the secondary winding is larger than the number of turns of the primary winding), the step-down transformer 55 (the number of turns of the secondary winding is the primary winding). The advantage of adding the capacitor 2 is greater than the case of using a smaller number of windings). In the case of the step-up type, since the current flowing in the circuit on the secondary side of the transformer 55 is small, the capacitance of the capacitor 2 can be reduced. Thus, when the step-up transformer 55 is employed, the capacitor 2 can be made cheaper and smaller than when the step-down transformer 55 is employed. Therefore, the efficiency can be increased without lowering the circuit scale and the circuit scale as compared with the switching power supply circuit 50.

  In the switching power supply circuit 50 shown in FIG. 5, the current flowing in the secondary circuit of the transformer 55 may oscillate due to resonance between the leakage inductor 56 and the capacitor 57. That is, when the relationship expressed by the following “Equation 1” is established, the current flowing in the secondary circuit of the transformer 55 oscillates.

  A is an integer. Further, fsw is a frequency of a reference signal for generating a drive signal for the switching element 52. Further, fs is a resonance frequency of a resonance circuit composed of the leakage inductor 56 and the capacitor 57, and is represented by the following “Equation 2”.

  Note that Lr is the inductance of the leakage inductor 56. Also, n is the winding ratio of the transformer 55. Cd is one of the capacitors 57-1 to 57-4.

  In general, the capacitor 57 of the switching power supply circuit 50 is composed of a parasitic element of the diode 58. Therefore, the capacitance of the capacitor 57 is very small, and the relationship of the above "Equation 1" is established.

  That is, since the capacity of the capacitor 57 is very small, the Q value of the resonance circuit composed of the leakage inductor 56 and the capacitor 57 becomes high as apparent from the following “Equation 3”.

  For this reason, the switching power supply circuit 50 has a problem that the peak value of the voltage applied to each diode 58 increases, and the rated voltage of each diode 58 must be increased. As described above, when the diode 58 having a large rated voltage is used, the conduction loss of the diode 58 increases and the loss of the entire switching power supply circuit 50 increases.

  However, this problem can be solved by making the capacitance Cs of the capacitor 2 larger than the capacitance Cd of the capacitor 57 in the switching power supply circuit 1 of the present embodiment. That is, by setting Cs> Cd, Q1 which is the Q value of the resonance circuit including the leakage inductor 56, the capacitor 2, and the capacitor 57 can be made smaller than the above-mentioned Q as shown in the following “Equation 4”.

  As described above, since the capacitance Cs of the capacitor 2 is made larger than the capacitance Cd of the capacitor 57, Q1 can be made smaller than Q. Therefore, the switching power supply circuit 1 is connected to the diode 58 in comparison with the switching power supply circuit 50. The peak value of the applied voltage can be lowered. As a result, the breakdown voltage of the diode 58 can be lowered, and the loss of the diode 58 can be reduced accordingly. Further, since the withstand voltage of the diode 58 can be lowered, an inexpensive diode 58 can be used, and the manufacturing cost of the entire switching power supply circuit 1 can be reduced. In addition, since the withstand voltage of the diode 58 can be lowered, a smaller diode 58 can be used, and the circuit scale of the entire switching power supply circuit 1 can be reduced.

  The capacitance Cs of the capacitor 2 is set so that the resonance frequency fs1 of the resonance circuit formed by the leakage inductor 56 and the capacitor 2 is larger than the frequency fsw of the reference signal for generating the drive signal for the switching element 52. It is desirable to make it larger than the capacitance Cd of the capacitor 57.

  This prevents the current Ip flowing through the primary side coil of the transformer 55 from proceeding more than the voltage VAB applied to the primary side coil of the transformer 55 and reducing the AC power supplied to the transformer 55. it can.

  FIG. 3 is a diagram for explaining a method of calculating the resonance frequency fs1, and FIG. 3A schematically shows a circuit on the primary side of the transformer 55 of the switching power supply circuit 1 in the period (I) shown in FIG. FIG.

As shown in FIG. 3A, in the period (I), the switching elements 52-1 and 52-4 are turned on, and a positive current Ip flows through the primary side coil 55-1 of the transformer 55. Since a positive voltage is applied to the primary coil 55-1 of 55, positive AC power is transmitted to the primary coil 55-1 of the transformer 55. Therefore, in the period (I), it can be considered that the capacitor 2 is connected in parallel to the primary side coil 55-1 of the transformer 55. At this time, the capacity of the capacitor 2 is n ² · Cs, where n is the winding ratio of the transformer 55.

FIG. 3B is a diagram showing an equivalent circuit of the circuit shown in FIG.
The circuit shown in FIG. 3B is configured by connecting an AC power supply 30, an inductor 31, and an inductor 32 in series, and connecting the inductor 32 and the capacitor 33 in parallel with each other. The inductor 31 corresponds to the leakage inductor 56, the inductor 32 corresponds to the primary coil 55-1 of the transformer 55, and the capacitor 33 corresponds to the capacitor 2. Further, it is assumed that the inductance Lm of the inductor 32 is sufficiently larger than the inductance Lr of the inductor 31.

  Therefore, the resonance frequency fs1 is obtained by the following “Equation 5” and “Equation 6” by the circuit shown in FIG. Ts1 is a resonance period of a resonance circuit composed of the leakage inductor 56 and the capacitor 2.

  That is, it is desirable that the capacitance Cs of the capacitor 2 be as large as possible without reducing the efficiency of the rated output power. As a result, the output power can be increased without reducing the efficiency of the rated output power.

  Further, the capacitance Cs of the capacitor 2 may be increased, and the inductance Lr of the leakage inductor 56 may be decreased. As a result, the voltage drop (Lr · di / dt) due to the leakage inductor 56 can be suppressed, so that the winding ratio of the transformer 55 can be further reduced, and the efficiency of the transformer 55 itself is improved and the transformer 55 is reduced in size. Can be

  In the above-described embodiment, the capacitor 2 is provided between the rectifier circuit 59 and the smoothing circuit 63. However, the rectifier circuit 59 and the smoothing circuit 63 are connected as two capacitors by connecting two or more capacitors in parallel. You may comprise so that it may provide between.

  Further, when the capacitor 2 is composed of two or more capacitors, the capacitor to be used among the two or more capacitors is a fluctuation in the power supply voltage of the DC power supply 53 (ie, DC power input to the conversion circuit 54) or a load. You may comprise so that it may select according to the fluctuation | variation of the direct-current power which 62 requires.

  FIG. 4 is a diagram showing a circuit in the vicinity of the capacitor 2 in the switching power supply circuit 1 when the capacitor 2 is composed of two or more capacitors. In addition, the same code | symbol is attached | subjected to the same structure as the structure shown in FIG.

  As shown in FIG. 4, the capacitor 2 is constituted by three capacitors 2-1 to 2-3. The capacitors 2-1 to 2-3 are connected to the drains of the switching elements 40-1 to 40-3 (IGBT (Insulated Gate Bipolar Transistor) in the example shown in FIG. 4) (switches). In addition, the switching elements 40-1 to 40-3 are turned on and off by a drive signal output from the control circuit 41, respectively.

  Here, the capacity of the capacitor 2-1 is 1000 [pF], the capacity of the capacitor 2-2 is 2000 [pF], the capacity of the capacitor 2-3 is 3000 [pF], and the power supply voltage of the DC power supply 53 is 100 [V]. ], 80 [V], 40 [V], and 20 [V].

  For example, when the power supply voltage of the DC power supply 53 is 100 [V], the control circuit 41 turns on the switching element 40-1, turns off the switching elements 40-2 and 40-3, and sets the capacitance of the capacitor 2 to 1000. [PF]. When the power supply voltage of the DC power supply 53 is 80 [V], the control circuit 41 turns on the switching element 40-2 and turns off the switching elements 40-1 and 40-3, so that the capacitance of the capacitor 2 is 2000. [PF]. When the power supply voltage of the DC power supply 53 is 40 [V], the control circuit 41 turns on the switching element 40-3, turns off the switching elements 40-1 and 40-2, and sets the capacitance of the capacitor 2 to 3000. [PF]. When the power supply voltage of the DC power supply 53 is 20 [V], the control circuit 41 turns on the switching elements 40-1 and 40-3, turns off the switching element 40-2, and sets the capacitance of the capacitor 2 to 4000. [PF].

  In this way, a predetermined capacitor is selected from two or more capacitors and the capacitance of the capacitor 2 is varied in accordance with fluctuations in DC power input to the conversion circuit 54 or fluctuations in DC power required by the load 62. Thus, the efficiency of the transformer 55 itself can be maintained even if the DC power input to the conversion circuit 54 or the DC power required by the load 62 varies. In addition, the efficiency of the transformer 55 can be increased over a wide output power range.

  In the above embodiment, the bridge constituted by the switching elements 52-1 and 52-2 is referred to as “advanced phase bridge”, and the bridge constituted by the switching elements 52-3 and 52-4 is referred to as “lagging phase bridge”. However, a bridge constituted by the switching elements 52-1 and 52-2 is referred to as a “lagging phase bridge”, and a bridge constituted by the switching elements 52-3 and 52-4 is also referred to as a “leading phase bridge”. Good.

  Even if comprised in this way, the effect similar to the said embodiment can be acquired.

It is a figure which shows the switching power supply circuit of embodiment of this invention. In the switching power supply circuit of this embodiment, it is a figure which shows the drive signal of a switching element, the electric current which flows into an AB section, and the voltage applied to an AB section. It is a figure for demonstrating the calculation method of the resonant frequency of the resonant circuit in the switching power supply circuit of this embodiment. It is a figure which shows a part of switching power supply circuit of other embodiment of this invention. It is a figure which shows the existing switching power supply circuit. It is a figure for demonstrating operation | movement of a conversion circuit. It is a figure which shows the flow of an electric current when the switching element is driving. It is a figure which shows the drive signal of a switching element, the electric current which flows into an AB section, and the voltage applied to an AB section in the existing switching power supply circuit.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Switching power supply circuit 2 Capacitor 30 AC power supply 31 Inductor 32 Inductor 33 Capacitor 40 Switching element 41 Control circuit 50 Switching power supply circuit 51 Capacitor 52 Switching element 53 DC power supply 54 Conversion circuit 55 Transformer 56 Leakage inductor 57 Capacitor 58 Diode 59 Rectifier circuit 60 Inductor 61 Capacitor 62 Load 63 Smoothing circuit 64 Capacitor

Claims (5)

The first capacitor is composed of first, second, third, and fourth switching elements connected in parallel, and the first switching element and the second switching element are the first switching element. A first phase bridge is formed in series so as to be on the high potential side, and the third switching element and the fourth switching element are connected in series so that the third switching element is on the high potential side. To form a second phase bridge, wherein the first and second switching elements are alternately turned on and off, and the third and fourth switching elements are alternately turned on and off, thereby providing direct current power. A conversion circuit that converts AC to AC power;
An inductor constituting a resonance circuit with the first capacitor;
A transformer that steps up or steps down AC power output from the conversion circuit via the inductor;
A rectifier circuit configured to rectify AC power output from the transformer, which is constituted by a diode;
A smoothing circuit for smoothing the output from the rectifier circuit,
The phase of the drive signal input to the first phase bridge is shifted with respect to the phase of the drive signal input to the second phase bridge, and each switching element is zero-volt switched by resonance of the resonance circuit. A switching power supply circuit,
A second capacitor is provided between the rectifier circuit and the smoothing circuit;
A switching power supply circuit. The switching power supply circuit according to claim 1,
The capacity of the second capacitor is set to be larger than the capacity of a third capacitor that is a parasitic element of the diode.
A switching power supply circuit. A switching power supply circuit according to claim 2,
The capacitance of the second capacitor is such that the resonance frequency of a resonance circuit composed of the inductor and the second capacitor is higher than the frequency of a reference signal for generating a drive signal for turning on / off each switching element. Set to be larger,
A switching power supply circuit. The switching power supply circuit according to any one of claims 1 to 3,
The capacitance of the second capacitor is varied according to fluctuations in DC power input to the conversion circuit or fluctuations in DC power required by a load provided at a subsequent stage of the smoothing circuit.
A switching power supply circuit. The switching power supply circuit according to any one of claims 1 to 3,
The second capacitor is composed of a plurality of capacitors connected in parallel to each other,
A switch for selecting a capacitor to be used among the plurality of capacitors;
A control circuit that operates the switch in response to fluctuations in DC power input to the conversion circuit or fluctuations in DC power required by a load provided in a subsequent stage of the smoothing circuit;
A switching power supply circuit comprising:

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