EP0193162A1 - Microwave bandpass filter - Google Patents

Microwave bandpass filter Download PDF

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Publication number
EP0193162A1
EP0193162A1 EP86102410A EP86102410A EP0193162A1 EP 0193162 A1 EP0193162 A1 EP 0193162A1 EP 86102410 A EP86102410 A EP 86102410A EP 86102410 A EP86102410 A EP 86102410A EP 0193162 A1 EP0193162 A1 EP 0193162A1
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EP
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Prior art keywords
resonators
filter
elements
resonator
line
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Granted
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EP86102410A
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German (de)
French (fr)
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EP0193162B1 (en
Inventor
Jean-Claude Cruchon
Gilbert Prost
Jean-Pierre Marquet
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Alcatel Transmission par Faisceaux Hertziens SA
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Alcatel Thomson Faisceaux Hertziens SA
Alcatel Transmission par Faisceaux Hertziens SA
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    • HELECTRICITY
    • H01ELECTRIC ELEMENTS
    • H01PWAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00Auxiliary devices
    • H01P1/20Frequency-selective devices, e.g. filters
    • H01P1/201Filters for transverse electromagnetic waves
    • H01P1/203Strip line filters

Definitions

  • the present invention relates to bandpass filters for microwave frequencies, and, in particular, broadband filters and filters produced with ribbon waveguides.
  • microwave bandpass filters for example in the technology of ribbon waveguides (stripline or microstrip in Anglo-Saxon literature), by combining in series a lowpass filter and a pass filter -high ;
  • the low-pass filter consists of a succession of sections of thin lines and sections of wide lines which respectively constitute the inductive and capacitive elements of the filter;
  • the high-pass filter comprises sections of thin lines connected to ground, which constitute set elements and which are connected to each other by open circuit lines or capacitors-
  • Such filters require a large number of poles in the pass filter -bas and in the high-pass filter, that is to say a large number of line sections; they are therefore bulky and expensive.
  • band-pass filters are produced by means of successive resonators, placed between the inlet and the outlet of the filter and very strongly coupled together; the resonators are very close to each other so as to obtain the strong coupling.
  • Such filters are difficult to manufacture, even in ribbon waveguide technology, when the desired coupling requires a space between two successive resonators of less than 100 microns; indeed, this coupling must be perfectly constant from one filter to another to maintain the same characteristics for all filters of the same production.
  • the object of the present invention is to avoid, or at least to reduce the aforementioned drawbacks.
  • a bandpass filter for microwave comprising, in series from the electrical point of view, n + 2 elements (n: positive integer) constituted by an input line, n linear resonators, open to both ends and all substantially of given length ⁇ b / 2 and an output line, the resonators being ordered from the first to the n me respectively between the input line and the output line, is characterized by the combination of n + capacitive couplings for coupling respectively the input line at the first end of the first resonator, the second ends of the i the resonators at the first ends of the (i + 1) my resonators (with i integer ranging from 1 inclusive to n-1 inclusive) and the second end from the n me resonator to the output line, and at least one pair of linear resonators of length ⁇ s / 4 - ( ⁇ s wavelength to reject, less than ab), the resonators of a pair each having one end connected to one of the n + 2 elements e t
  • FIG. 1 represents a filter according to the invention: this filter, produced in waveguides with ribbons, comprises a support, P, made of polytetrafluoroethylene glass (better known under the registered trademark "teflon glass") constituted by a rectangular plate 45 x 65 mm and 1.6 mm thick.
  • the hidden face of the support P is entirely covered by a copper deposit which constitutes a ground plane; on the visible side of the copper deposits A, 1 to 7, 10, 11, 70, 71, B respectively constitute an input line, seven linear resonators open at their two ends, four linear, auxiliary, short-circuit resonators at one of their ends and an exit line.
  • the filter according to FIG. 1 is a filter of the type with parallel lines, in fact the resonators 1 to 7 are constituted by sections of lines in parallel to reduce the size of the filter; these sections are arranged between the input and output lines, A and B.
  • the resonators 1 to 7 are resonators of the half-wave line type, all substantially of length ⁇ b / 2 or ⁇ b is the wavelength corresponding to the center frequency of the filter bandwidth.
  • variable capacitors CO to C7 respectively connect line A to the first end of the resonator 1, the second end of the resonator 1 at the first end of the resonator 2, ..., the second end of the resonator 6 at the first end of the resonator 7 and the second end of the resonator 7 at line B; the line sections 1 to 7, with the capacitors C1 to C6, thus form a zigzag assembly.
  • auxiliary resonators 10, 11, 70, 71, of quarter-wave line type are mounted in short circuit by connection of one of their ends to the resonator 1 for 10 and 11 and to the resonator 7 for 70 and 71.
  • These short-circuit resonators are intended to provide a notch function in the filter so that, as will appear in FIG. 2, the amplitude / frequency response curve of the filter has a bandwidth with a steeper edge in high frequency limit; for this the length of these auxiliary resonators is chosen to be equal to X s / 4 where X s is a wavelength to be rejected, less than ⁇ b and corresponding substantially to the central frequency of the frequency band to be eliminated by the cut function -bandaged.
  • auxiliary resonators are associated in pairs, 10-11 and 70-71 and the resonators of the same pair are arranged at a distance equal to (2 k + 1 ) ⁇ b / 4 from each other with k positive integer taken, in the example described, equal to 1; the choice of this distance between the auxiliary resonators allows mutual compensation, in the bandwidth of the filter, of the inductive and capacitive disturbances brought by each of the resonators of the same pair.
  • the auxiliary resonators of this cut-off function strip can practically be arranged in any place of the electrical path which connects the two accesses of the filter, as long as, between them, the distance of (2k + 1) ⁇ b / 4 is respected.
  • the filter which has just been described has a bandwidth at 3 decibels which goes from 950 to 1700 MHz with, on both sides, a rapid attenuation up to 30 decibels.
  • FIG. 2 is a graphic representation of amplitude / frequency responses relating to the circuit of figure 1.
  • Three curves, G1, G2, G3, have been represented.
  • the answer is that sought for the low frequencies but, on the side of the high frequencies, the attenuation is not fast enough and strong enough.
  • the curve G3 relates to the amplitude / frequency response of the circuit described using FIG. 1; the comparison of this curve with the curve G2 shows that the addition of the notch filter, presenting a cut band centered on approximately 2300 MHz and obtained thanks to the quarter wave lines whose resonance frequencies are chosen in the band 1850 -2500 MHz, has the effect of causing a sudden loss variation near the high frequencies of the bandpass filter: loss of less than 3 decibels below 1750 MHz and loss of the order of 20 to 30 decibels for frequencies from 1800 MHz to more than 2500 MHz; this attenuation becomes less important again for frequencies of the order of 2700 MHz and more, but these frequencies are sufficiently distant from the frequencies of the passband (950-1700 MHz) so that it can result in a drawback in the majority of cases use of the filter.
  • FIG. 1 Another embodiment of a filter according to the invention is described with the aid of Figures 3 to 5; it is in fact a filter having the same characteristics as the filter according to FIG. 1 but produced in two layers plus a ground plane on flexible supports and in which the capacitors corresponding to the capacitors C1 to C6 of FIG. 1, are obtained by overlapping the ends of lines separated by the thickness of a flexible support.
  • Figure 3 shows a flexible support in polyamide, S1, on which five copper deposits have been made: A, 1 + 1 0 and 11, 3, 5, 7 + 70 and 71, B.
  • Figure 4 shows another flexible polyamide support, S2, on which three copper deposits have been made: 2, 4, 6.
  • the supports S1 and S2 are two rectangular plates of 35 x 144 mm which are then glued to each other, to give the assembly shown in Figure 5; under the plates S1 and S2 is also bonded a ground plane constituted by a polyamide support covered, on a surface, by a copper deposit; this ground plane is not visible in FIG. 5.
  • the input and output lines are designated respectively by the letters A and B while the resonators in half-wave lines have the marks 1 to 7 and that the resonators, in quarter lines d wave, of the notch function, bear the marks 10, 11, 70, 71.
  • the capacitive couplings between the line A and the resonator 1 and between the resonator 7 and the line B are respectively provided by the capacitors CO and C7 .
  • the couplings between the half-wave resonators are obtained by placing the ends to be coupled face to face; the facing surfaces, separated by the dielectric from the polyamide support, thus form the two plates of the coupling capacitors; these capacitors bear the references C1 to C6 in FIG. 5.
  • the filter can be designed in a tri-plate structure, that is to say with the resonators arranged in the space separating two parallel ground planes.
  • the capacitors C1 to C7 can be obtained by means of metal tongues deposited on a dielectric substrate; these tabs are arranged so that, for example to replace the capacitor C1 of FIG. 1, the two ends of the tab are respectively opposite the ends of the resonators 1 and 2 to which the capacitor C1 was connected; the facing surfaces determine the coupling between the successive resonators.
  • Capacitors such as CO and C7 can also be obtained by this technique of facing copper surfaces or by that presented in Figure 5; or equivalent; this is possible by giving the ends opposite sufficient surfaces taking into account the thickness and the permittivity of the dielectric which separates them and the capacity to obtain.

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Abstract

Filtre passe-bande réalisé avec des guides d'ondes à ruban et facilement reproductible. Le filtre comporte, entre ses deux accès (A, B), n résonateurs demi-onde (1-7) montés en série. Des condensateurs (C0-C7) assurent un fort couplage entre les éléments successifs de ce montage en série. Des résonateurs quart d'onde (10, 11, 70, 71), reliés par une de leurs extrémités au montage série, assurent, en limite de la bande passante du filtre ainsi obtenu, une réponse amplitude/fréquence à front raide. Application aux filtres passe-bande, à large bande, pour hyperfréquences.Bandpass filter made with ribbon waveguides and easily reproducible. The filter comprises, between its two ports (A, B), n half-wave resonators (1-7) connected in series. Capacitors (C0-C7) ensure a strong coupling between the successive elements of this series connection. Quarter-wave resonators (10, 11, 70, 71), connected by one of their ends to the series circuit, provide, at the limit of the passband of the filter thus obtained, an amplitude / frequency response with a steep edge. Application to band pass filters, wide band, for microwave frequencies.

Description

La présente invention concerne les filtres passe-bande pour hyperfréquences, et, en particulier, les filtres à large bande et les filtres réalisés avec des guides d'ondes à rubans.The present invention relates to bandpass filters for microwave frequencies, and, in particular, broadband filters and filters produced with ribbon waveguides.

Il est connu de réaliser des filtres passe-bande en hyperfréquences, par exempte dans la technologie des guides d'ondes à rubans (stripline ou microstrip dans la littérature anglo-saxonne), en associant en série un filtre passe-bas et un filtre passe-haut ; le filtre passe-bas est constitué d'une succession de tronçons de lignes minces et de tronçons de lignes larges qui constituent respectivement les éléments selfiques et capacitifs du filtre ; le filtre passe-haut comporte des tronçons de lignes minces connectés à la masse, qui constituent des éléments setfiques et qui sont reliés entre eux par des lignes en circuit ouvert ou des condensateurs- De tels filtres nécessitent un nombre de pôles important dans le filtre passe-bas et dans le filtre passe-haut, c'est-à-dire un nombre important de tronçons de lignes ; ils sont donc encombrants et chers.It is known to produce microwave bandpass filters, for example in the technology of ribbon waveguides (stripline or microstrip in Anglo-Saxon literature), by combining in series a lowpass filter and a pass filter -high ; the low-pass filter consists of a succession of sections of thin lines and sections of wide lines which respectively constitute the inductive and capacitive elements of the filter; the high-pass filter comprises sections of thin lines connected to ground, which constitute set elements and which are connected to each other by open circuit lines or capacitors- Such filters require a large number of poles in the pass filter -bas and in the high-pass filter, that is to say a large number of line sections; they are therefore bulky and expensive.

D'autres filtres passe-bande connus sont réalisés au moyen de résonateurs successifs, disposés entre l'entrée et la sortie du filtre et très fortement couplés entre eux ; les résonateurs sont très proches les uns des autres de manière à obtenir le fort couplage. De tels filtres sont difficiles à fabriquer, même dans la technologie des guides d'ondes à rubans, quand le couplage désiré nécessite un espace entre deux résonateurs successifs inférieur à 100 microns ; en effet ce couplage doit être parfaitement constant d'un filtre à l'autre pour conserver les mêmes caractéristiques à tous les filtres d'une même production.Other known band-pass filters are produced by means of successive resonators, placed between the inlet and the outlet of the filter and very strongly coupled together; the resonators are very close to each other so as to obtain the strong coupling. Such filters are difficult to manufacture, even in ribbon waveguide technology, when the desired coupling requires a space between two successive resonators of less than 100 microns; indeed, this coupling must be perfectly constant from one filter to another to maintain the same characteristics for all filters of the same production.

La présente invention a pour but d'éviter, ou pour le moins, de réduire les inconvénients précités.The object of the present invention is to avoid, or at least to reduce the aforementioned drawbacks.

Ceci est obtenu principalement grâce à un filtre à résonateurs dans lequel d'une part le couplage entre les résonateurs successifs est renforcé à l'aide de condensateurs convenablement disposés, et dans lequel d'autre part une fonction stop-bande a été introduite.This is obtained mainly thanks to a resonator filter in which on the one hand the coupling between the successive resonators is reinforced by means of suitably arranged capacitors, and in which on the other hand a band-stop function has been introduced.

Selon l'invention, un filtre passe-bande pour hyperfréquences, comportant, en série du point de vue électrique, n+2 éléments (n : nombre entier positif) constitués par une ligne d'entrée, n résonateurs linéaires, ouverts à leurs deux extrémités et tous sensiblement de longueur λ b/2 donnée et une ligne de sortie, les résonateurs étant ordonnés du premier au n me entre respectivement la ligne d'entrée et la ligne de sortie, est caractérisé par la combinaison de n+ couplages capacitifs pour coupler respectivement la ligne d'entrée à la première extrémité du premier résonateur, les secondes extrémités des i les résonateurs aux premières extrémités des (i+1) mes résonateurs (avec i entier allant de 1 compris à n-1 compris) et la seconde extrémité du n me résonateur à la ligne de sortie, et d'au moins une paire de résonateurs linéaires de longuer λ s/4 - (λ s longueur d'onde à réjeter, inférieure à ab), les résonateur d'une paire ayant chacun une extrémité reliée à l'un des n + 2 éléments et étant à une distance électrique -

Figure imgb0001
l'un de l'autre (avec k entier supérieur à -1).According to the invention, a bandpass filter for microwave, comprising, in series from the electrical point of view, n + 2 elements (n: positive integer) constituted by an input line, n linear resonators, open to both ends and all substantially of given length λ b / 2 and an output line, the resonators being ordered from the first to the n me respectively between the input line and the output line, is characterized by the combination of n + capacitive couplings for coupling respectively the input line at the first end of the first resonator, the second ends of the i the resonators at the first ends of the (i + 1) my resonators (with i integer ranging from 1 inclusive to n-1 inclusive) and the second end from the n me resonator to the output line, and at least one pair of linear resonators of length λ s / 4 - (λ s wavelength to reject, less than ab), the resonators of a pair each having one end connected to one of the n + 2 elements e t being at an electrical distance -
Figure imgb0001
from each other (with k integer greater than -1).

La présente invention sera mieux comprise et d'autres caractéristiques apparaîtront à l'aide de la description ci-après et des figures s'y rapportant qui représentent :

  • -la figure 1, un premier exemple de filtre selon l'invention,
  • -la figure 2, des courbes de réponse en fréquence, relatives au filtre selon la figure 1,
  • -les figures 3 à 5, des vues relatives à un second exemple de filtre selon l'invention.
The present invention will be better understood and other characteristics will appear with the aid of the description below and of the figures relating thereto which represent:
  • FIG. 1, a first example of a filter according to the invention,
  • FIG. 2, frequency response curves, relating to the filter according to FIG. 1,
  • FIGS. 3 to 5, views relating to a second example of a filter according to the invention.

Sur les différentes figures les éléments correspondants sont désignés par les mêmes repères.In the various figures, the corresponding elements are designated by the same references.

La figure 1 représente un filtre selon l'invention : ce filtre, réalisé en guides d'ondes à rubans, comporte un support, P, en verre polytétrafluoroéthylène (plus connu sous la marque déposée "verre teflon") constitué par une plaque rectangulaire de 45 x 65 mm et de 1,6 mm d'épaisseur. La face cachée du support P est entièrement recouverte par un dépôt de cuivre qui constitue un plan de masse ; sur la face visible des dépôts de cuivre A, 1 à 7, 10, 11, 70, 71, B constituent respectivement une ligne d'entrée, sept résonateurs linéaires ouverts à leurs deux extrémités, quatre résonateurs linéaires, auxiliaires, en court-circuit à une de leurs extrémités et une ligne de sortie. Il est à noter que, dans cette description et dans les revendications, il est question de filtres ayant une ligne d'entrée, telle que A sur la figure 1 et une ligne de sortie telle que B sur cette même figure, mais bien entendu le rôle de ces lignes peut être inversé, la ligne A devenant alors l'accès de sortie et la ligne B l'accès d'entrée. Le filtre selon la figure 1 est un filtre du type à lignes parallèles, en effet les résonateurs 1 à 7 sont constitués par des tronçons de lignes en parallèle pour diminuer l'encombrement du filtre ; ces tronçons sont disposés entre les lignes d'entrée et de sortie, A et B. Les résonateurs 1 à 7 sont des résonateurs du type ligne demi-onde, tous sensiblement de longueur λ b/2 ou λ b est la longueur d'onde correspondant à la fréquence centrale de la bande passante du filtre. Pour obtenir un couplage important entre les tronçons successifs de ce filtre et faire que ce couplage soit facilement reproductible d'un filtre à l'autre d'une même production, des condensateurs variables CO à C7 relient respectivement la ligne A à la première extrémité du résonateur 1, la seconde extrémité du résonateur 1 à la première extrémité du résonateur 2, ... , la seconde extrémité du résonateur 6 à la première extrémité du résonateur 7 et la seconde extrémité du résonateur 7 à la ligne B ; les tronçons de lignes 1 à 7, avec les condensateurs C1 à C6, forment ainsi un ensemble en zigzag.FIG. 1 represents a filter according to the invention: this filter, produced in waveguides with ribbons, comprises a support, P, made of polytetrafluoroethylene glass (better known under the registered trademark "teflon glass") constituted by a rectangular plate 45 x 65 mm and 1.6 mm thick. The hidden face of the support P is entirely covered by a copper deposit which constitutes a ground plane; on the visible side of the copper deposits A, 1 to 7, 10, 11, 70, 71, B respectively constitute an input line, seven linear resonators open at their two ends, four linear, auxiliary, short-circuit resonators at one of their ends and an exit line. It should be noted that, in this description and in the claims, it is a question of filters having an input line, such as A in FIG. 1 and an output line such as B in this same figure, but of course the role of these lines can be reversed, line A then becoming the exit access and line B the entry access. The filter according to FIG. 1 is a filter of the type with parallel lines, in fact the resonators 1 to 7 are constituted by sections of lines in parallel to reduce the size of the filter; these sections are arranged between the input and output lines, A and B. The resonators 1 to 7 are resonators of the half-wave line type, all substantially of length λ b / 2 or λ b is the wavelength corresponding to the center frequency of the filter bandwidth. To obtain a significant coupling between the successive sections of this filter and to make this coupling easily reproducible from one filter to another of the same production, variable capacitors CO to C7 respectively connect line A to the first end of the resonator 1, the second end of the resonator 1 at the first end of the resonator 2, ..., the second end of the resonator 6 at the first end of the resonator 7 and the second end of the resonator 7 at line B; the line sections 1 to 7, with the capacitors C1 to C6, thus form a zigzag assembly.

Les quatre résonateurs auxiliaires 10, 11, 70, 71, de type ligne quart d'onde, sont montés en court-circuit par branchement de l'une de leurs extrémités sur le résonateur 1 pour 10 et 11 et sur le résonateur 7 pour 70 et 71. Ces résonateurs en court-circuit sont destinés à amener une fonction coupe-bande dans le filtre afin, comme il apparaîtra sur la figure 2, que la courbe de réponse amplitude/fréquence du filtre présente une bande passante à flanc plus raide en limite des fréquences hautes ; pour cela la longeur de ces résonateurs auxiliaires est choise égale à X s/4 où X s est une longueur d'onde à rejeter, inférieur à λ b et correspondant sensiblement à la fréquence centrale de la bande de fréquences à éliminer par la fonction coupe-bande. Ces résonateurs auxiliaires sont associés par paires, 10-11 et 70-71 et les résonateurs d'une même paire sont disposés à une distance égale à (2 k+1) λ b/4 l'un de l'autre avec k entier positif pris, dans l'exemple décrit, égal à 1 ; le choix de cette distance entre les résonateurs auxiliaires permet une compensation mutuelle, dans la bande passante du filtre, des perturbations selfiques et capacitives amenées par chacun des résonateurs d'une même paire. Il est par ailleurs à noter que les résonateurs auxiliaires de cette fonction coupe-bande peuvent pratiquement être disposés en n'importe quel endroit du trajet électrique qui relie les deux accès du filtre, dans la mesure où, entre eux, la distance de (2k + 1 ) λ b/4 est respectée. Le filtre qui vient d'être décrit présente une bande passante à 3 décibels qui va de 950 à 1700 MHz avec, de part et d'autre, un affaiblissement rapide jusqu'à 30 décibels.The four auxiliary resonators 10, 11, 70, 71, of quarter-wave line type, are mounted in short circuit by connection of one of their ends to the resonator 1 for 10 and 11 and to the resonator 7 for 70 and 71. These short-circuit resonators are intended to provide a notch function in the filter so that, as will appear in FIG. 2, the amplitude / frequency response curve of the filter has a bandwidth with a steeper edge in high frequency limit; for this the length of these auxiliary resonators is chosen to be equal to X s / 4 where X s is a wavelength to be rejected, less than λ b and corresponding substantially to the central frequency of the frequency band to be eliminated by the cut function -bandaged. These auxiliary resonators are associated in pairs, 10-11 and 70-71 and the resonators of the same pair are arranged at a distance equal to (2 k + 1 ) λ b / 4 from each other with k positive integer taken, in the example described, equal to 1; the choice of this distance between the auxiliary resonators allows mutual compensation, in the bandwidth of the filter, of the inductive and capacitive disturbances brought by each of the resonators of the same pair. It should also be noted that the auxiliary resonators of this cut-off function strip can practically be arranged in any place of the electrical path which connects the two accesses of the filter, as long as, between them, the distance of (2k + 1) λ b / 4 is respected. The filter which has just been described has a bandwidth at 3 decibels which goes from 950 to 1700 MHz with, on both sides, a rapid attenuation up to 30 decibels.

Là figure 2 est une représentation graphique de réponses amplitude/fréquence relatives au circuit de la figure 1. Trois courbes, G1, G2, G3, ont été représentées.There figure 2 is a graphic representation of amplitude / frequency responses relating to the circuit of figure 1. Three curves, G1, G2, G3, have been represented.

La courbe G1 est relative au circuit de la figure 1 avec des condensateurs de couplage CO à C7 de forte valeur - (CO et C7 = 20 pF et C1 à C6 = 5 pF) et sans les résonateurs auxiliaires 10, 11, 70, 71 ; cette courbe est sensiblement celle d'un filtre passe-haut dont l'atténuation, supérieure à 30 décibels en dessous de 200 MHz, passe de 30 à 1 décibel entre 200 et 500 MHz, est de l'ordre de 1 à 2 décibels entre 500 et 1600 MHz (réponse plate) puis varie environ de 1 à 11 décibels dans le reste des fréquences où a été effectuée la mesure, c'est-à-dire entre 1600 et 3750 MHz. Cette réponse en fréquences est loin de correspondre à la bande passante du filtre de la figure 1 : 950 -1700 MHz.The curve G1 relates to the circuit of FIG. 1 with coupling capacitors CO to C7 of high value - (CO and C7 = 20 pF and C 1 to C6 = 5 pF) and without the auxiliary resonators 10, 11, 70, 71; this curve is substantially that of a high-pass filter whose attenuation, greater than 30 decibels below 200 MHz, goes from 30 to 1 decibel between 200 and 500 MHz, is of the order of 1 to 2 decibels between 500 and 1600 MHz (flat response) then varies from approximately 1 to 11 decibels in the rest of the frequencies where the measurement was made, that is to say between 1600 and 3750 MHz. This frequency response is far from corresponding to the bandwidth of the filter in Figure 1: 950-1700 MHz.

La courbe G2 de la figure 2 est relative à la réponse amplitude/ fréquence du circuit de la figure 1 sans les résonateurs auxiliaires 10, 11, 70, 71 mais avec les condensateurs CO à C7 tels qu'ils sont réglés dans le filtre (CO et C7 = 15 pF, C1 et C6 = 3 pF, C2 à C5 = 1,5 pF). La réponse est celle recherchée pour les fréquences basses mais, du côté des fréquences hautes, l'atténuation n'est pas assez rapide et assez forte.The curve G2 in FIG. 2 relates to the amplitude / frequency response of the circuit of FIG. 1 without the auxiliary resonators 10, 11, 70, 71 but with the capacitors CO to C7 as they are set in the filter (CO and C7 = 15 pF, C1 and C6 = 3 pF, C2 to C5 = 1.5 pF). The answer is that sought for the low frequencies but, on the side of the high frequencies, the attenuation is not fast enough and strong enough.

La courbe G3 est relative à la réponse amplitude/fréquence du circuit décrit à l'aide de la figure 1 ; la comparaison de cette courbe avec la courbe G2 montre que l'adjonction du filtre coupe-bande, présentant une bande de coupure centrée sur environ 2300 MHz et obtenue grâce aux lignes quart d'onde dont les fréquences de résonance sont choisies dans la bande 1850-2500 MHz, a pour effet d'entraîner une variation d'affaiblissement brusque au voisinage des fréquences hautes du filtre passe-bande : affaiblissement de moins de 3 décibels en dessous de 1750 MHz et affaiblissement de l'ordre de 20 à 30 décibels pour des fréquences de 1800 MHz à plus de 2500 MHz ; cet affaiblissement redevient moins important pour des fréquences de l'ordre de 2700 MHz et plus, mais ces fréquences sont suffisamment éloignées des fréquences de la bande passante (950-1700 MHz) pour qu'il puisse en résulter un inconvénient dans la majorité des cas d'utilisation du filtre.The curve G3 relates to the amplitude / frequency response of the circuit described using FIG. 1; the comparison of this curve with the curve G2 shows that the addition of the notch filter, presenting a cut band centered on approximately 2300 MHz and obtained thanks to the quarter wave lines whose resonance frequencies are chosen in the band 1850 -2500 MHz, has the effect of causing a sudden loss variation near the high frequencies of the bandpass filter: loss of less than 3 decibels below 1750 MHz and loss of the order of 20 to 30 decibels for frequencies from 1800 MHz to more than 2500 MHz; this attenuation becomes less important again for frequencies of the order of 2700 MHz and more, but these frequencies are sufficiently distant from the frequencies of the passband (950-1700 MHz) so that it can result in a drawback in the majority of cases use of the filter.

Un autre exemple de réalisation d'un filtre selon l'invention est décrit à l'aide des figures 3 à 5 ; il s'agit en fait d'un filtre ayant les mêmes caractéristiques que le filtre selon la figure 1 mais réalisé en deux couches plus un plan de masse sur supports souples et dans lequel les condensateurs correspondant aux condensateurs C1 à C6 de la figure 1, sont obtenus par chevauchement d'extrémités de lignes séparées par l'épaisseur d'un support souple.Another embodiment of a filter according to the invention is described with the aid of Figures 3 to 5; it is in fact a filter having the same characteristics as the filter according to FIG. 1 but produced in two layers plus a ground plane on flexible supports and in which the capacitors corresponding to the capacitors C1 to C6 of FIG. 1, are obtained by overlapping the ends of lines separated by the thickness of a flexible support.

La figure 3 montre un support souple en, polyamide, S1, sur lequel ont été effectués cinq dépôts de cuivre : A, 1 +10 et 11, 3, 5, 7 + 70 et 71, B. La figure 4 montre un autre support souple en polyamide, S2, sur lequel ont été effectués trois dépôts de cuivre : 2, 4, 6. Les supports S1 et S2 sont deux plaques rectangulaires de 35 x 144 mm qui sont ensuite collées l'une sur l'autre, pour donner l'assemblage représenté sur la figure 5 ; sous les plaques S1 et S2 est également collé un plan de masse constitué par un support en polyamide recouvert, sur une surface, par un dépôt cuivreux ; ce plan de masse n'est pas visible sur la figure 5.Figure 3 shows a flexible support in polyamide, S1, on which five copper deposits have been made: A, 1 + 1 0 and 11, 3, 5, 7 + 70 and 71, B. Figure 4 shows another flexible polyamide support, S2, on which three copper deposits have been made: 2, 4, 6. The supports S1 and S2 are two rectangular plates of 35 x 144 mm which are then glued to each other, to give the assembly shown in Figure 5; under the plates S1 and S2 is also bonded a ground plane constituted by a polyamide support covered, on a surface, by a copper deposit; this ground plane is not visible in FIG. 5.

A l'ensemble constitué par les plaques S1 et S2 avec leurs dépôts et le plan de masse il suffit d'ajouter deux condensateurs miniatures fixes, de 15 picofarads chacun, CO, C7, pour constituer un filtre comparable au filtre de la figure 1. Comme dans le filtre de la figure 1, les lignes d'entrée et de sortie sont désignées respectivement par les lettres A et B tandis que les résonateurs en lignes demi-onde portent les repères 1 à 7 et que les résonateurs, en lignes quart d'onde, de la fonction coupe-bande, portent les repères 10, 11, 70, 71. Les couplages capacitifs entre la ligne A et le résonateur 1 et entre le résonateur 7 et la ligne B sont respectivement assurés par les condensateurs CO et C7. Par contre les couplages entre les résonateurs demi-onde sont obtenus par mise face à face des extrémités à coupler ; les surfaces en regard, séparées par le diélectrique du support en polyamide, forment ainsi les deux plaques des condensateurs de couplages ; ces condensateurs portent les références C1 à C6 sur la figure 5.To the assembly constituted by the plates S1 and S2 with their deposits and the ground plane, it suffices to add two fixed miniature capacitors, of 15 picofarads each, CO, C7, to constitute a filter comparable to the filter of FIG. 1. As in the filter of FIG. 1, the input and output lines are designated respectively by the letters A and B while the resonators in half-wave lines have the marks 1 to 7 and that the resonators, in quarter lines d wave, of the notch function, bear the marks 10, 11, 70, 71. The capacitive couplings between the line A and the resonator 1 and between the resonator 7 and the line B are respectively provided by the capacitors CO and C7 . On the other hand, the couplings between the half-wave resonators are obtained by placing the ends to be coupled face to face; the facing surfaces, separated by the dielectric from the polyamide support, thus form the two plates of the coupling capacitors; these capacitors bear the references C1 to C6 in FIG. 5.

Différentes autres réalisations d'un filtre passe-bande sont possibles sans sortir du cadre de l'invention. C'est ainsi, en particulier, que le filtre peut être conçu en structure tri-plaque c'est-à-dire avec les résonateurs disposés dans l'espace séparant deux plans de masse parallèles. De même, à partir de réalisation selon la figure 1, les condensateurs C1 à C7 peuvent être obtenus grâce à des languettes métalliques déposées sur un sùbstrat en diélectrique ; ces languettes sont disposées de manière que, par exemple pour remplacer le condensateur C1 de la figure 1, les deux extrémités de la languette soient respectivement en regard des extrémités des résonateurs 1 et 2 sur lesquelles était connecté le condensateur C1 ; les surfaces en regard déterminent le couplage entre les résonateurs successifs. Des condensateurs tels que CO et C7 (figures 1 et 5) peuvent également être obtenus par cette technique de surfaces de cuivre en regard ou par celle qui est présentée à la figure 5 ; ou un équivalent ; c'est possible en donnant aux extrémités en regard des surfaces suffisantes compte tenu de l'épaisseur et de la permittivité du diélectrique qui les sépare et de la capacité à obtenir.Various other embodiments of a bandpass filter are possible without departing from the scope of the invention. Thus, in particular, the filter can be designed in a tri-plate structure, that is to say with the resonators arranged in the space separating two parallel ground planes. Similarly, from the embodiment according to FIG. 1 , the capacitors C1 to C7 can be obtained by means of metal tongues deposited on a dielectric substrate; these tabs are arranged so that, for example to replace the capacitor C1 of FIG. 1, the two ends of the tab are respectively opposite the ends of the resonators 1 and 2 to which the capacitor C1 was connected; the facing surfaces determine the coupling between the successive resonators. Capacitors such as CO and C7 (Figures 1 and 5) can also be obtained by this technique of facing copper surfaces or by that presented in Figure 5; or equivalent; this is possible by giving the ends opposite sufficient surfaces taking into account the thickness and the permittivity of the dielectric which separates them and the capacity to obtain.

Il est également possible de réaliser un filtre ne comportant qu'un seul résonateur de type demi-onde et une seule paire de résonateurs quart d'onde.It is also possible to produce a filter comprising only a single half-wave resonator and a single pair of quarter-wave resonators.

Claims (2)

1. Filtre passe-bande pour hyperfréquences, comportant, en série du point de vue électrique, n + 2 éléments (n : nombre entier positif) constitués par un ligne d'entrée (A), n résonateurs linéaires (1 -7), ouverts à leurs deux extrémités et tous sensiblement de longueur λ b/2 donnée et une ligne de sortie (B), les résonateurs étant ordonnés du premier au n meentre respectivement la ligne d'entrée et la ligne de sortie, caractérisé par la combinaison de n + 1 couplages capacitifs (CO-C7) pour coupler respectivement la ligne d'entrée (A) à la première extrémité du premier résonateur (1), les secondes extrémités des i mes résonateurs aux premières extrémités des (i+1) mes résonateurs (avec i entier allant de 1 compris à n-1 compris) et la seconde extrémité du n me résonateur (7) à la ligne de sortie (B), et d'au moins une paire de résonateurs linéaires (10-11, 70-71) de longueur λ s/4 (Xs longueur d'onde à rejeter, inférieure à Xb), les résonateurs d'une paire ayant chacun une extrémité reliée à l'un des n+2 éléments (A, 1-7, B) et étant à une distance électrique
Figure imgb0002
l'un de l'autre (avec k entier supérieur à -1).
1. Bandpass filter for microwave, comprising, in series from the electrical point of view, n + 2 elements (n: positive integer) constituted by an input line (A), n linear resonators (1 -7), open at their two ends and all substantially of given length λ b / 2 and an output line (B), the resonators being ordered from the first to the n me between the input line and the output line respectively, characterized by the combination of n + 1 capacitive couplings (CO-C7) to respectively couple the input line (A) to the first end of the first resonator (1), the second ends of the i resonators to the first ends of the (i + 1 ) my resonators (with i being an integer from 1 inclusive to n-1 inclusive) and the second end of me n resonator (7) to the output line (B), and at least a pair of linear resonators (10-11, 70 -71) of length λ s / 4 (Xs wavelength to reject, less than Xb), the resonators of a pair each having one end connected to one of the n + 2 elements (A, 1-7, B) and being at an electrical distance
Figure imgb0002
from each other (with k integer greater than -1).
2. Filtre selon la revendication 1, dans lequel les n+2 éléments sont réalisés selon la technique des guides d'ondes à rubans, caractérisé en ce que les n+ éléments (A, 1-7, B) sont répartis de part et d'autre d'un même support en diélectrique (S1) et en ce que au moins un (C1-C6) des n+ couplages capacitifs entre deux éléments (1-2, 2-3, 3-4, 4-5, 5-6, 6-7) est obtenu par mise face à face d'une extrémité d'un des deux éléments considérés avec une extrémité de l'autre des deux éléments considérés, les deux éléments considérés étant, pour cela, disposés de part et d'autre du support et la surface de leurs extrémités en regard étant déterminée en fonction de la capacité à obtenir (figure 5).2. Filter according to claim 1, in which the n + 2 elements are produced according to the technique of ribbon waveguides, characterized in that the n + elements (A, 1 -7, B) are distributed on both sides and d '' of the same dielectric support (S1) and in that at least one (C1-C6) of the n + capacitive couplings between two elements (1-2, 2-3, 3-4, 4-5, 5- 6, 6-7) is obtained by placing one end of one of the two elements considered face to face with one end of the other of the two elements considered, the two elements considered being, for this purpose, arranged on both sides 'other support and the surface of their opposite ends being determined according to the ability to obtain (Figure 5).
EP86102410A 1985-02-27 1986-02-25 Microwave bandpass filter Expired - Lifetime EP0193162B1 (en)

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FR8502850A FR2578104B1 (en) 1985-02-27 1985-02-27 BAND PASS FILTER FOR MICROWAVE
FR8502850 1985-02-27

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0368661A2 (en) * 1988-11-11 1990-05-16 Matsushita Electric Industrial Co., Ltd. Microwave filter
EP0373028A1 (en) * 1988-11-30 1990-06-13 Thomson Hybrides Passive band-pass filter
ES2091713A2 (en) * 1994-02-15 1996-11-01 Follente Emilio Diez Pass-band filter network based on the induction of reverse currents in printed line segments
EP0800224A3 (en) * 1996-04-01 1998-07-29 Matsushita Electric Industrial Co., Ltd. Receiving apparatus

Families Citing this family (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH0432803Y2 (en) * 1986-05-08 1992-08-06
FR2613557A1 (en) * 1987-03-31 1988-10-07 Thomson Csf FILTER COMPRISING CONSTANT DISTRIBUTED ELEMENTS ASSOCIATING TWO TYPES OF COUPLING
US5231349A (en) * 1988-05-20 1993-07-27 The Board Of Trustees Of The Leland Stanford Junior University Millimeter-wave active probe system
JPH0728163B2 (en) * 1988-11-11 1995-03-29 松下電器産業株式会社 Microwave filter
JPH0728162B2 (en) * 1988-11-11 1995-03-29 松下電器産業株式会社 Microwave filter
US7231238B2 (en) 1989-01-13 2007-06-12 Superconductor Technologies, Inc. High temperature spiral snake superconducting resonator having wider runs with higher current density
GB2246670B (en) * 1990-08-03 1995-04-12 Mohammad Reza Moazzam Microstrip coupled lines filters with improved performance
US5138288A (en) * 1991-03-27 1992-08-11 Motorola, Inc. Micro strip filter having a varactor coupled between two microstrip line resonators
JPH07106815A (en) * 1993-08-09 1995-04-21 Oki Electric Ind Co Ltd Strip line resonator
GB2382233A (en) * 2001-08-08 2003-05-21 Koninkl Philips Electronics Nv Hybrid filter
WO2003026059A1 (en) * 2001-09-20 2003-03-27 Paratek Microwave, Inc. Tunable filters having variable bandwidth and variable delay
US7034636B2 (en) * 2001-09-20 2006-04-25 Paratek Microwave Incorporated Tunable filters having variable bandwidth and variable delay
JP3766791B2 (en) * 2001-10-12 2006-04-19 シャープ株式会社 High frequency filter circuit and high frequency communication device
US20030222732A1 (en) * 2002-05-29 2003-12-04 Superconductor Technologies, Inc. Narrow-band filters with zig-zag hairpin resonator
JP4565145B2 (en) * 2005-09-02 2010-10-20 独立行政法人情報通信研究機構 Ultra-wideband bandpass filter
JP4565146B2 (en) * 2005-09-06 2010-10-20 独立行政法人情報通信研究機構 Multiband ultra wideband bandpass filter
TWI352447B (en) * 2008-01-04 2011-11-11 Hon Hai Prec Ind Co Ltd Ultra wide-band filter
TW201212371A (en) * 2010-09-10 2012-03-16 Universal Scient Ind Shanghai Micro band-pass filter
FR2977382A1 (en) * 2011-06-29 2013-01-04 Thomson Licensing HIGH REJECTION BAND STOP FILTER AND DUPLEXER USING SUCH FILTERS
US9467116B2 (en) * 2011-12-19 2016-10-11 Intel Corporation Broad band diplexer using suspended strip-line capacitor technology

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE1925610A1 (en) * 1968-05-29 1969-12-04 Marconi Co Ltd Filter arrangement consisting of a microwave filter
EP0071509A1 (en) * 1981-07-24 1983-02-09 Thomson-Csf Band-pass filter with open-ended linear resonators
FR2525835A1 (en) * 1982-04-27 1983-10-28 Thomson Csf BAND PASS FILTER WITH LINEAR RESONATORS, TO WHICH A BAND CUTTER FUNCTION IS ASSOCIATED
US4418324A (en) * 1981-12-31 1983-11-29 Motorola, Inc. Implementation of a tunable transmission zero on transmission line filters

Family Cites Families (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE1591581C3 (en) * 1967-10-12 1975-10-23 Siemens Ag, 1000 Berlin Und 8000 Muenchen Microwave shadow circle in triplate technology
US3605045A (en) * 1969-01-15 1971-09-14 Us Navy Wide-band strip line frequency-selective circuit
JPS5275951A (en) * 1975-12-20 1977-06-25 Matsushita Electric Ind Co Ltd Microwave circuit equipment
JPS5370739A (en) * 1976-12-07 1978-06-23 Fujitsu Ltd Blocking filter for strip line band
DE2714181A1 (en) * 1977-03-30 1978-10-05 Siemens Ag Microwave filter with resonators in interdigital structure - has additional resonators before and after input and output resonators to give additional finite frequency attenuation peak
FR2431773A1 (en) * 1978-07-21 1980-02-15 Thomson Csf MICROWAVE FILTER WITH DIELECTRIC RESONATORS AND TELECOMMUNICATIONS EQUIPMENT PROVIDED WITH SUCH A FILTER
FR2510325B1 (en) * 1981-07-24 1987-09-04 Thomson Csf SMALL DIMENSIONAL MICROWAVE FILTER WITH LINEAR RESONATORS
JPS58166803A (en) * 1982-03-27 1983-10-03 Fujitsu Ltd Dielectric filter
JPS5974701A (en) * 1982-10-20 1984-04-27 Murata Mfg Co Ltd Filter device
JPS58223902A (en) * 1982-06-21 1983-12-26 Nippon Telegr & Teleph Corp <Ntt> Strip resonator
JPS5986306A (en) * 1982-11-09 1984-05-18 Toshiba Corp Band-pass filter
FR2540294B1 (en) * 1983-01-31 1985-10-04 Thomson Csf MICROWAVE FILTER WITH LINEAR RESONATORS
JPS59191902A (en) * 1983-04-15 1984-10-31 Hitachi Ltd Filter

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE1925610A1 (en) * 1968-05-29 1969-12-04 Marconi Co Ltd Filter arrangement consisting of a microwave filter
EP0071509A1 (en) * 1981-07-24 1983-02-09 Thomson-Csf Band-pass filter with open-ended linear resonators
US4418324A (en) * 1981-12-31 1983-11-29 Motorola, Inc. Implementation of a tunable transmission zero on transmission line filters
FR2525835A1 (en) * 1982-04-27 1983-10-28 Thomson Csf BAND PASS FILTER WITH LINEAR RESONATORS, TO WHICH A BAND CUTTER FUNCTION IS ASSOCIATED

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, vol. MTT-22, no. 5, mai 1974, pages 499-504, IEEE, New York, US; E.G. CRISTAL et al.: "A compact channel-dropping filter for stripline and microwave integrated circuits" *
IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, vol. MTT-31, no. 5, mai 1983, pages 397-402, IEEE, New York, US; C.I. MOBBS et al.: "A generalized chebyshev suspended substrate stripline bandpass filter" *

Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0368661A2 (en) * 1988-11-11 1990-05-16 Matsushita Electric Industrial Co., Ltd. Microwave filter
EP0368661A3 (en) * 1988-11-11 1990-11-28 Matsushita Electric Industrial Co., Ltd. Microwave filter
US5015976A (en) * 1988-11-11 1991-05-14 Matsushita Electric Industrial Co., Ltd. Microwave filter
EP0373028A1 (en) * 1988-11-30 1990-06-13 Thomson Hybrides Passive band-pass filter
FR2648641A2 (en) * 1988-11-30 1990-12-21 Thomson Hybrides PASSIVE FILTER BAND-PASTE
ES2091713A2 (en) * 1994-02-15 1996-11-01 Follente Emilio Diez Pass-band filter network based on the induction of reverse currents in printed line segments
EP0800224A3 (en) * 1996-04-01 1998-07-29 Matsushita Electric Industrial Co., Ltd. Receiving apparatus
US6072999A (en) * 1996-04-01 2000-06-06 Matsushita Electric Industrial Co., Ltd. Receiving apparatus

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EP0193162B1 (en) 1990-06-13
NO169366C (en) 1992-06-10
NO169366B (en) 1992-03-02
FR2578104B1 (en) 1987-03-20
DE3672035D1 (en) 1990-07-19
US4731596A (en) 1988-03-15
NO860694L (en) 1986-08-28
FR2578104A1 (en) 1986-08-29

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