TWI513367B - Electronic control gears for led light engine and application thereof - Google Patents

Description

Electronic control device for LED light engine and its application

The invention relates to a light-emitting diode (LED) light engine control device, in particular to comparing a current detecting resistor with a reference voltage different from each comparing circuit by using a comparison circuit, and adjusting an operating state of the corresponding bypass switch to step by step. The LED light engine electronic control unit of the LED sub-array is turned on or off step by step.

Light-emitting diodes have a higher luminous efficacy than conventional luminaires. Traditional bulbs provide about 15 lumens per watt, while light-emitting diodes (LEDs) have up to 100 lumens per watt (lumens) Above watt), and the light-emitting diode has the advantages of long life, no external interference and no damage, and is the first choice for lighting equipment.

Generally speaking, the light-emitting diode needs to be driven by a direct current, and the commercial power is an alternating current, which must be converted into a direct current through a rectifier (full-wave or half-wave rectification) before being supplied to the light-emitting diode for use. The converted DC pulse signal, in the vicinity of the initial and end sections of each cycle (ie, dead time), cannot overcome the forward voltage drop of the LED to drive the LED. This results in a narrow conduction angle and a low power factor. The dead time refers to a period during which the LED stops conducting, and the conduction angle refers to a period during which the LED is turned on. The sum of the conduction angle and the dead time is a rectified DC pulse wave. shape. The longer the dead time, the narrower the conduction angle and the lower the power factor. Traditional LED drivers typically face the following three problems.

The first problem is that conventional LED drivers require filters, rectifiers, and more complex driver circuits such as power factor correctors (PFCs), resulting in high drive cost. At the same time, although the life of the light-emitting diode is long, the electrolytic capacitor used in the power factor corrector is easily damaged, so that the overall life is relatively shortened, and the advantages of the light-emitting diode cannot be exhibited.

The second problem is that at no-load time, no current passes through the light-emitting diode, causing a flicker phenomenon of the lighting device. During the DC pulse period, the LED is driven by the forward current and is illuminated, and then driven by the zero current to extinguish. When there is no dead time, the LED will cause flicker between lighting and extinction. The frequency of the general city AC power is 60 Hz. After rectification, a DC voltage pulse is formed, the frequency is twice (about 120 Hz), and the flicker phenomenon occurs at a no-load time at a frequency of about 120 Hz. The flickering phenomenon caused by the dead time is not easy to be perceived by the human eye, but it is easy to cause eye fatigue.

The third problem is the low power factor. The low power power factor corrector has a loop current that is too weak to be accurately detected and corrects the AC input current to a sine wave waveform. The power factor can be calculated by dividing the input power by the product of the input voltage (line voltage) and the input current (line current) (PF = P / (V × I), where PF is the power factor, P is the input power, V And I is the effective value of the line voltage and the line current, respectively, to measure the efficiency of the use of electricity. When the similarity between the line voltage and the line current is higher, the power use efficiency is better, and the power factor is higher. When the line voltage and the line current waveform are almost identical, at this time, the power factor has a maximum value of approximately 1.

The traditional power factor corrector needs to detect the current in the loop, so that the corrected line current waveform is closer to the line voltage waveform. If the current in the loop is too low to be correctly detected by the current detection circuit of the power factor corrector, the power factor corrector will not be able to properly line current and line. The waveform of the voltage is aligned with the phase to achieve a better power factor. Due to the discontinuity of the AC input current waveform and the total harmonic distortion (THD) caused by the jump point, the dead time is related to the dead time. According to the Fourier analysis for the development of the periodic signal, any discontinuity or jump point in the periodic waveform will result in higher-order harmonics on the basic components, resulting in an increase in total harmonic distortion. Therefore, eliminating discontinuities and jumping points will help reduce total harmonic distortion.

In view of this, how to simplify the circuit and process complexity, maintain good power factor and low harmonic distortion is one of the main topics for the development of light-emitting diode light sources.

The LED light engine electronic control device proposed by the invention uses a comparison circuit to transmit a current detecting resistance, detects a voltage across the current sub-voltage of the LED sub-array, and compares with a reference voltage different from each comparison circuit to regulate Corresponding to the operating state of the bypass switch, the LED light-emitting diode electronic control device of the LED sub-array is turned on step by step or stepwise.

An electronic control device for an LED light engine according to an embodiment of the invention includes a rectifier, a current regulator, a current regulate switch column, and a switch control circuit. The rectifier is used to connect an external AC voltage source to provide a DC pulse voltage. The current regulator is used to adjust the input current wave to form a quasi-sinusoidal square wave or step wave waveform, which effectively increases the power factor. The bypass switch column is coupled to the rectifier and disposed in parallel with an external LED array. The external LED array includes a plurality of LED sub-arrays connected in series, and each of the bypass switches may be a transistor (for example, a gold-oxygen half field effect transistor). The bypass switch column includes a plurality of bypass switches connected in series to bypass the corresponding LED sub-array when turned on. The switch control circuit has a current detecting resistor and a plurality of comparison circuits. The current detecting resistor is coupled between the cathode and the ground of the external LED array, and is coupled to each of the comparators. The reference terminals of the circuit respectively have different reference voltages, and the comparison circuits respectively compare the voltages of the current detecting resistors with the reference voltages, and adjust the corresponding bypass switches to be turned off or on, and the current detecting resistors The voltage across the voltage is related to the DC pulse voltage, so that the bypass switch column illuminates the LED sub-arrays in sections according to the DC pulse voltage. The number of bypass switches is, for example, less than the number of external LED sub-arrays.

An electronic control device for an LED light engine according to another embodiment of the present invention includes a rectifier, a current regulate switch column, and a switch control circuit. The rectifier is used to connect an external AC voltage source to provide a DC pulse voltage. The bypass switch column is coupled to the rectifier and disposed in parallel with an external LED array. The external LED array includes a plurality of LED sub-arrays connected in series, and each of the bypass switches may be a transistor (for example, a gold-oxygen half field effect transistor). The bypass switch column includes a plurality of bypass switches connected in series to bypass the corresponding LED sub-array when turned on. The switch control circuit has a current detecting resistor and a plurality of comparing circuits. The current detecting resistor is coupled between the cathode and the ground of the external LED array, and is coupled to the reference end of each comparing circuit, and the comparing circuits respectively have different The reference voltage, and the comparison circuits are respectively compared with the reference voltages according to the voltage across the current detecting resistors, and the corresponding bypass switches are turned off or turned on, and the voltage across the current detecting resistors is related to the DC pulse voltage, so as to bypass The switch column illuminates the LED sub-arrays in sections according to the DC pulse voltage. The number of bypass switches is, for example, equal to the number of external LED sub-arrays.

The bypass switch in the embodiment of the present invention is, for example, a depleted or enhanced transistor, which can be regulated by a switch control circuit, and according to the input AC voltage, when the voltage is increased, the LED sub-array is driven step by step, and the line is stepwise increased. Current; when the voltage is reduced, the LED sub-array is extinguished step by step, and the line current is reduced step by step, simplifying the circuit, improving the luminous efficiency, improving the power factor, and reducing the cost.

A current detecting resistor according to an embodiment of the present invention includes a shared current sensing and modulation unit coupled to an external LED array for planning the current of the illuminated external LED sub-array to adjust the illuminated external LED. The brightness of the sub-array, wherein the shared current sensing and modulation unit comprises a potentiometer, a voltage controlled resistor or a transistor switch. In one embodiment, at least one of a pulse width modulation unit, a low pass filter, and a voltage follower is further included. The electronic control device of the LED light engine can be manually dimmed (mechanical dimming) via the shared current sensing and modulation unit, or dimmed by the shared current sensing and modulation unit by using the dimming signal ( Electronically controlled dimming).

An embodiment of the present invention further includes a voltage regulator array including a plurality of voltage regulators coupled between the input voltage and the comparison circuit for stabilizing the turn-on voltage of the bypass switch, such that the bypass switch The on state is not affected by the falling edge of the input voltage of the DC pulse.

In an embodiment of the invention, a sinusoidal voltage compensator is coupled between the input voltage and the switch control circuit for extracting the input voltage of the DC pulse to compensate the voltage waveform of the LED through the LED. The voltage waveform is modified by a step wave to a waveform closer to the sine wave, further improving the power factor.

In an embodiment of the invention, a line regulation tightener is further coupled to the current regulator. The line voltage regulation rate compactor includes a shunt regulator (or a two-carrier junction transistor) for voltage detection, and is coupled to the input voltage through a voltage detection voltage dividing resistor. When the input voltage overcomes the forward voltage drop of all LED sub-arrays, but the reference voltage of the parallel regulator or voltage detection bipolar junction transistor of the voltage detection has not been overcome, the current through the LED sub-array is the first a current, when the input voltage overcomes the forward voltage drop across all of the LED sub-arrays, and overcomes the double-carrier connection of the voltage regulator's shunt regulator or voltage detection When the reference voltage of the surface transistor is used, the current through the LED sub-array is the second current, and the first current is greater than the second current.

In an embodiment of the present invention, a plurality of flicker-suppression capacitors and a plurality of diodes are respectively connected, and each of the flicker suppression capacitors is respectively connected in parallel to the corresponding one or more external LED sub-arrays, and each of the two The cathode of the pole body is coupled to the anode of the corresponding outer LED sub-array. When the input voltage still only overcomes the forward voltage drop of the external LED sub-array below the current level and below, the flicker suppression capacitor discharges to illuminate the external LED sub-array above the level.

AC‧‧‧AC voltage source

100‧‧‧Rectifier

120‧‧‧current regulator

140a, 145a, 146a, 148a, 140b, 140c‧‧‧ line voltage regulation rate reducer

142‧‧‧Control circuit

160‧‧‧current sense resistor

160a, 160b, 160c, 160d‧‧‧ shared current sensing and modulation unit

180, 182, 184‧‧ ‧ voltage regulator

C1, C2, C3, C4, Cf, Cg1, Cg2, Cg3, Cg4, Cg1', Cg2', Cg3', Cg4'‧‧‧ capacitor

150, 152, 154‧‧‧ comparison circuit

F‧‧‧Voltage Follower

PWM‧‧‧ pulse width modulation unit

Rp, R15, R16, Rx, Rx1, Rx2, Rx3, Rx4, Ra, Ra1, Ra2, Ra3, Ra4, Rm1, Rm2, Rg1, Rg2, Rg3, Rx, Rx1, Rx2, Rx3, Rz1, Rz2, Rz3, Rk1, Rk2, Rk3, Rk4, Re1, Re2, Re3, Re4, Rj1, Rj2, Rj3, Rj4, Rf1, Rf2, Rf3, Rf4, Rf5, Rf6, Rf7, Rf8, Rt1, Rt2, Rt3, Rt4, Rt5, Rt6, Rt7, R50, R52, R54, Rd1, Rd2, Rd3, Rp4, Rp5, Rp6, Rv1, Rv2, Rv3‧‧‧ resistance

R1, R2‧‧‧ sinusoidal voltage compensator

G‧‧‧External LED subarray

G1, G2, G3, G4‧‧‧ LED sub-arrays

S1, S2, S3, S4, S10, S20, S30, S15, S25, S35‧‧‧ bypass switch

Z1, Z2, Z3, Z4, Z5, Z6, Zd1, Zd2, Zd3, Ze, Zk, Zf1, Zf2‧‧‧ Zener diode

Dx, Dg1, Dg2, Dg3, Dg4, D1, D2, D3, D4, D5, D6‧‧‧ diode

Dp‧‧‧Light diode

X1, X2, X3, X, Xe, Xf, Xh, Xk‧‧‧ shunt regulator

M, Me, Mj, Mk, M16, Mf1, Mf2, B1, B2, B3, B7, B8, B9, B10, B16, Bf, P1, P2, P3, P4, P5, P6, Bh, Bp‧‧ Transistor

Pf‧‧‧Opto-coupling components

Vcc‧‧‧ voltage source

Vin‧‧‧Input voltage

Iin‧‧‧ input current

I _LED ‧‧‧current through the LED sub-array

T, T’‧‧‧ cycle

t, t1', t0, t1, t2, t3, t4, t4', t4 ₁ , t4 ₂ , t5, t5', t5 ₁ , t5 ₂ , t6, t7, t8, t9‧‧

I0, I1, I2, I3, I4, I4 ^L , I4 ^M , I4 ^H ‧‧‧ Current

Maximum value of Lmax, Lmax'‧‧‧ light output waveform

Minimum value of Lmin, Lmin'‧‧‧ light output waveform

Lave, Lave’s average light output

A, B, A’, B’‧‧‧ area

Figure 1A is a schematic illustration of the circuit architecture of a lighting device in accordance with the present invention. The illumination device includes an electronic control device including a current regulator, an LED light engine, and an external LED array (divided into a plurality of light emitting diode sub-arrays).

FIG. 1B is a schematic diagram showing another circuit architecture of a lighting device in accordance with the present invention. The illuminating device is an electronic control device of another LED light engine that does not include a current regulator and an external LED array.

2A-2B is a specific circuit diagram of an electronic control device of the LED light engine of FIG. 1A. The bypass switch is an N-channel depletion-mode metal oxide semiconductor field effect transistor (NDMOSFET). 2A-2B differ in whether the comparison circuit of the switch control circuit passes through the dual-carrier junction transistor, and the bypass switch is turned on or off.

3A-3B are schematic diagrams showing another specific circuit of the electronic control device of the LED light engine of FIG. 1A. The difference from FIGS. 2A-2B is that the comparison circuit includes a bi-carrier junction transistor to switch the bypass switch on or off.

4A-4D illustrate an electronic control device of the LED light engine of FIG. 1A. The current detecting resistor further includes a shared current sensing and modulation unit to achieve a dimming function.

5A-5B are schematic views of an electronic control unit of the LED light engine in accordance with FIG. 1A. The difference from FIGS. 2A to 2B is that the bypass switch corresponds to an n-channel enhancement-mode metal oxide semiconductor field effect transistor (NEMOSFET). The difference between Figures 5A and 5B is that the bypass switch is switched on or off by a diode or a bipolar junction transistor.

6A-6B are schematic diagrams showing a specific circuit of an electronic control device of the LED light engine of FIG. 1A. The difference from FIGS. 5A to 5B is that the comparison circuit includes a bipolar junction transistor.

7A-7B are schematic diagrams showing a specific circuit of an electronic control device of the LED light engine of FIG. 1A. The difference from FIG. 5A, FIG. 6B is that the electronic control device of the LED light engine further includes a voltage regulator array including a plurality of voltage regulating circuits for stabilizing the conduction state of the bypass switch. The voltage regulator array is suitable for the circuit structure of any of the foregoing embodiments.

8A-8G are schematic diagrams showing the electronic control device of the LED light engine of FIG. 1A, which further includes different line voltage regulation rate reducers.

9A and 9B are graphs showing waveforms of the input voltage and the current through the LED sub-array relative to the time axis before and after the line voltage regulation rate tightener of the different embodiments are set.

Figure 10A is a circuit diagram showing an embodiment of an electronic control unit of the LED light engine of Figure 1A. The electronic control device of the LED light engine includes a plurality of scintillation suppression capacitors and a plurality of diodes, each of which is respectively connected in parallel with the corresponding external LED sub-array, and the cathodes of the respective diodes are coupled to the corresponding external LEDs. The anode of the array.

Figure 10B is a circuit diagram showing another embodiment of an electronic control unit of the LED light engine of Figure 1A. The electronic control device of the LED light engine includes a plurality of flicker suppression capacitors And a plurality of diodes, each of the scintillation suppression capacitors is respectively connected in parallel with one or more corresponding external LED sub-arrays in series, and the cathodes of the respective diodes are coupled to the anodes of the corresponding external LED sub-arrays.

FIG. 10C is a graph showing the waveforms of the input voltage, the input current, the current through the LED sub-array, and the light output intensity with respect to the time axis before and after the setting of the scintillation suppression capacitor and the diode of FIG. 10A or FIG. 10B.

Generally, the output voltage of the AC power source is a sinusoidal waveform, and after being rectified by the rectifier, the pulse voltage of the pulsed DC waveform of the first half of the sine wave is applied to the LED lighting device.

At the beginning of the first half of each cycle and the low voltage section at the end of the second half, the input voltage cannot overcome the forward voltage drop of the LED, and no current flows, forming a dead time. In addition, LED lighting devices are typically constructed from LED sub-arrays. When the number of LEDs connected in series is large, the total forward voltage drop is increased, so that the dead time becomes larger, the conduction angle becomes narrower, and the power factor is lowered.

For the problem of narrow conduction angle, the conventional solution is to use a power factor corrector to push the rectified AC voltage to a DC voltage value that is higher than the sum of the forward voltage drops of all LED sub-arrays. However, the electrolytic capacitor used in the power factor corrector is easily damaged, so that the light-emitting diode cannot perform the intended effect.

A lighting strategy in accordance with an embodiment of the present invention is to cut an array of LEDs into a plurality of sub-arrays of LEDs. The electronic control device of the LED light engine formed by the bypass switch and the switch control circuit illuminates the LED sub-array step by step as the input voltage rises in the first half cycle of the cycle, and the line current is gradually increased; After a period of one cycle, as the input voltage decreases, the LED sub-array is extinguished step by step, thereby increasing the conduction angle and modifying the current waveform.

In addition, the brightness of the LED can be adjusted by adjusting the current through the LED. That is, when there are multiple segments of the LED sub-array that need to be dimmed, the resistance values of the segments of the LED sub-arrays can be adjusted in stages, thereby changing the current through each segment of the LED sub-array to adjust the brightness of each segment of the LED. However, such a dimming mechanism is not easy to implement on a circuit structure, and requires high manufacturing cost and manufacturing difficulty. In particular, the more the number of segments of the LED sub-array, the higher the manufacturing cost and difficulty of the circuit. Therefore, the dimming strategy of an embodiment of the present invention, that is, an electronic control device for providing a dimmable LED light engine with a simplified dimming mechanism, can achieve the effect of segmental dimming only by using a current sensing resistor.

Referring to FIG. 1A, the electronic control device of the LED light engine includes a rectifier 100, a current regulator 120, a bypass switch column (including a plurality of bypass switches S1, S2, and S3), and a switch control circuit including comparison. Circuits 150, 152 and 154 and a current-sense resistor 160. The comparison circuits 150, 152, and 154 have, for example, a three-terminal structure, which may be a shunt regulator or a bi-carrier junction transistor, and the comparison circuits 150, 152, and 154 each have a first end, a second end, and a reference end. The reference terminals of the comparison circuits 150, 152, and 154 are respectively coupled to the current detecting resistor 160 through anti-clamping resistors Rx1, Rx2, and Rx3, so as to prevent the voltage across the current detecting resistor 160 from being clamped in comparison. The reference voltage Vref, _{3 of the} circuit 154. The second ends of the comparison circuits 150, 152, and 154 respectively control the bypass switches S1, S2, and S3. In addition to the last stage comparison circuit 154, the first end of the comparison circuit (eg, comparison circuit 150) of the upper stage is coupled to the lower stage comparison circuit through a Zener diode (eg, Zener diode Zd1) (eg, for comparison) Reference end of circuit 152). The bypass switches S1, S2, and S3 are, for example, gold oxide half field effect transistors or junction field effect transistors. The rectifier 100 is used to connect an external AC voltage source to provide a DC pulse voltage. A current regulator 120 is coupled to the external LED array G, and the external LED array G includes external LED sub-arrays G1 G G4.

The mechanism of action of the comparison circuits 150, 152, and 154 is described herein. In the embodiment, it is assumed that the comparison circuits 150, 152 and 154 have substantially the same reference voltage Vref, ₁ = Vref, ₂ = Vref, ₃ = Vref, and the Zener diodes Zd1 and Zd2 have substantially the same breakdown voltage. Vz, ₁ = Vz, ₂ = Vz. The comparison circuit 154 compares its reference voltage (ie, the reference voltage Vref) with the voltage across the sense resistor 160; the comparison circuit 152 compares its reference voltage (the reference voltage of the comparison circuits 154 and 152 with the breakdown voltage of the Zener diode Zd2). And, that is, 2Vref+Vz) and the voltage across the sense resistor 160; the comparison circuit 150 compares the reference voltage (the sum of the reference voltages of the comparison circuits 154, 152, and 150 and the breakdown voltages of the Zener diodes Zd2 and Zd1, That is, 3Vref+2Vz) and the voltage across the sense resistor 160. The reference voltages Vref, ₁ , Vref, ₂ and Vref, ₃ are positive values (Vref, ₁ , Vref, ₂ , Vref, ₃ > 0) greater than 0, and the reference voltages Vref, ₁ , Vref, ₂ and Vref, ₃ Can be equal to each other (both Vref) or unequal, and the breakdown voltages Vz,1 and Vz,2 of the Zener diodes Zd1 and Zd2 are positive values greater than or equal to 0 (Vz,1,Vz,2≧0) , indicating that the Zener diode Zd1 or Zd2 is selectively connected, and Vz, 1 and Vz, 2 may be equal to each other (all are Vz) or unequal, and are not limited. When the voltage received by the reference terminal of the comparison circuit 150, 152 or 154 is greater than its reference voltage, the comparison circuit 150, 152 or 154 is turned "on". When the voltage received by the reference terminal of the comparison circuit 150, 152 or 154 is less than its reference voltage, the comparison circuit 150, 152 or 154 is turned off. By turning on or off the comparison circuit 150, 152 or 154, the turn-off or conduction of the bypass switch can be controlled correspondingly. As long as the reference voltages Vref, ₁ , Vref, ₂ and Vref, ₃ are positive values greater than 0 (Vref, ₁ , Vref, ₂ , Vref, ₃ > 0) and the breakdown voltages Vz of the Zener diodes Zd1 and Zd2, 1 and Vz, 2 are positive values (Vz, 1, Vz, 2≧0) greater than or equal to 0, which necessarily satisfy the following general inequalities Vref, 1+Vref, 2+Vref, 3+Vz, 1+Vz, 2 >Vref, 1+Vref, 2+Vz, 2>Vref,1, to smoothly illuminate the LED sub-array step by step or step by step.

In one embodiment, the comparison circuits 150, 152, and 154 are, for example, shunt regulators or bipolar junction transistors. The reference poles of the comparison circuits 150, 152 and 154 respectively pass through the anti-clamp resistor Rx1, Rx2 and Rx3 detect the voltage across the current detecting resistor 160, so that the comparison circuit is turned on or off correspondingly, thereby controlling the operating states of the bypass switches S1 to S3.

The following describes the principle of lighting or extinguishing the LED sub-array. During the first half of the input voltage during the positive half cycle, the input voltage (vi) gradually increases from zero. When the input voltage has not overcome the forward voltage drop of the last stage LED sub-array (vi < V _G4 ), no current flows through the loop of the LED sub-array G4, the comparison circuit 154 fails to generate a voltage control signal, and the bypass switches S1, S2, and S3 The initial state is maintained (for example, if it is a depleted transistor, the initial state is an on state). As the input voltage rises to overcome the forward voltage drop of the final stage LED sub-array G4 (vi > V _G4 ), but has not overcome the sum of the forward voltage drops of the final secondary LED sub-arrays G4 and G3 (vi < V _G3 +V _G4 ), the current is lit by the bypass switch S1~S3 to the LED sub-array G4, and passes through the current detecting resistor 160, and the voltage across the current detecting resistor 160 reaches the reference voltage of the comparing circuit 154, so that the comparing circuit 154 is turned on. The bypass switch S3 is turned off, and then, the current through the current detecting resistor 160 is lowered, the comparison circuit 154 is turned off, and the bypass switch S3 is turned on again. In this stage, the bypass switch S3 quickly switches between the on and off states, which is called an adjustment state ( Regulating state), whereby the current through the LED sub-array G4 is regulated to be I1. At this time, the bypass switches S1 and S2 are all in an on state.

The voltage continues to rise to overcome the forward voltage drop (V _G3 +V _G4 ) below the final secondary LED sub-arrays G3 and G4, the bypass switch S2 is originally in an on state, and the current passes through the bypass switches S1, S2 to the LED sub-array G3 and LED sub-array G4, then the comparison circuit 152 detects the voltage across the current detecting resistor 160, generates a voltage control signal and turns off the bypass switch S2, so that the bypass switch S2 maintains the regulated state during this phase (fast switching between conduction and The off state) is used to regulate the current through the LED sub-arrays G3 and G4 to be I2. At this time, the bypass switch S1 maintains the on state, and the comparison circuit 154 detects the voltage across the current detecting resistor 160, generates a voltage control signal, and constantly turns off the bypass switch S3 to turn the bypass switch S3 into the off state.

When the input voltage continues to rise to overcome the forward voltage drop (V _G2 + V _G3 + V _G4 ) below the LED sub-array G2, the bypass switch S1 is originally in an on state, and the current passes through the bypass switch S1 to the LED sub-array G2, LED The sub-array G3 to the LED sub-array G4, the comparison circuit 150 detects the voltage across the current detecting resistor 160, generates a voltage control signal, and turns off the bypass switch S1, so that the bypass switch S1 maintains the regulated state during this phase (fast switching conduction) And the off state), thereby regulating the current through the LED sub-arrays G2, G3, and G4 to be I3. Further, after the comparison circuit 152 and the comparison circuit 154 detect the voltage across the current detecting resistor 160, the bypass switch S2 and the bypass switch S3 are also constantly turned off.

Until the input voltage rises to overcome the forward voltage drop (V _G1 + V _G2 + V _G3 + V _G4 ) below the LED sub-array G1, at this time, the comparison circuit 150 detects the voltage across the current detecting resistor 160 to generate voltage control. The signal is turned off the bypass switch S1, and the current rectified by the rectifier 100 is regulated by the current regulating circuit 120 to be I4 to be directly supplied to the LED array G to illuminate the LED sub-array G1 to the LED sub-array G4. At this stage, the comparison circuit 150, the comparison circuit 152, and the comparison circuit 154 keep the bypass switches S1 to S3 in an off state. According to the above manner, the electronic control unit of the LED light engine can illuminate the LED sub-array step by step in the direction of the LED sub-array G4 toward the LED sub-array G1 according to the rise of the input voltage in the first half of the cycle.

During the second half of the input voltage during the positive half cycle, the input voltage gradually decreases. When the input voltage (vi) continues to fall to the inability to overcome the forward voltage below the LED sub-array G1 (vi < V _G1 + V _G2 + V _G3 + V _G4 ), the forward voltage below the LED sub-array G2 can still be overcome ( When vi>V _G2 +V _G3 +V _G4 ), the voltage across the current detecting resistor 160 is insufficient to turn on the comparison circuit 150, and the bypass switch S1 does not receive the regulation signal of the comparison circuit 150 and is switched back to the on state from the off state. Then, the input current is slightly increased, and the comparison circuit 150 detects the voltage across the current detecting resistor 160 through the anti-clamping resistor Rx1 and then turns on, so that the bypass switch S1 is turned off. The bypass switch S1 switches between on and off and enters the regulation state so as to regulate the loop current through the LED sub-arrays G2, G3, and G4 to be I3. At this time, the bypass switch S2 and the bypass switch S3 are still in the off state. Similarly, when the input voltage continues to drop to overcome the forward voltage drop below the LED sub-array G2, it still overcomes the forward voltage drop below the LED sub-array G3 (V _G3 + V _G4 <vi < V _G2 + V _G3 + V _G4 ), the comparison circuit 152 switches the bypass switch S2 from the off state to the on state, then the current rises, the comparison circuit 152 is turned on, the bypass switch S2 is turned off again, and the bypass switch S2 is switched between the off and the conduction. Enter the adjustment state. At this time, the comparison circuit 152 controls the bypass switch S2 to continuously switch the off and on states to enter the regulation state, thereby regulating the loop current of the LED sub-arrays G3 and G4 that are lit by being I2.

In this manner, the comparison circuits 154, 152, and 150 respectively detect the voltage across the current sense resistor 160 and compare with the reference voltages of the comparison circuits 154, 152, and 150 (the reference voltages of the comparison circuits 154, 152, and 150 have been defined). Previously, the LED sub-array is extinguished step by step from the LED sub-array G1 toward the LED sub-array G4 until the end of the cycle, and then one cycle is repeated, and thus cycles.

FIG. 1B is a schematic diagram showing the circuit architecture of an electronic control unit of another LED light engine. The difference from FIG. 1A is that the electronic control unit of the LED light engine does not include a current regulator. The comparison circuit 156, the comparison circuit 154, the comparison circuit 152, and the comparison circuit 150 detect the voltage value across the voltage across the current detecting resistor 160, thereby regulating the bypass switch S3, the bypass switch S2, the bypass switch S1, and the bypass switch S0. The state is to provide a fixed current I1 for lighting the LED sub-array G4, to illuminate the LED sub-arrays G3 to G4 to be a fixed current I2, to illuminate the LED sub-arrays G2 to G4 to be a fixed current I3, to illuminate the LED sub-arrays G1 to G4 Is the fixed current I4. The presence or absence of the current regulator 120 affects the number of comparison circuits, and the number of the above elements is exemplified in the specification for convenience of explanation and is not intended to limit the present invention.

The embodiment shown in FIG. 2A is a specific circuit diagram of the electronic control device of the LED light engine of FIG. 1A. The current regulator 120 includes a transistor switch M (for example, a gold oxide half field effect transistor), a starting resistor Ra, a shunt regulator X (or a bipolar transistor), and a detecting resistor Rx. The current regulator 120 can be used to adjust the input current wave to form a sinusoidal wave or a waveform of the step wave, effectively increasing the power factor. The shunt regulators X1, X2 and X3 correspond to the comparison circuit 150, the comparison circuit 152 and the comparison circuit 154 of FIG. 1A, and the shunt regulators X1, X2 and X3 are respectively used for the voltage received by the reference terminal and the reference voltage of each comparison circuit. For comparison, the operational states of the bypass switches S10, S20, and S30 are switched. The bypass switch corresponds to an N-channel depletion-mode metal oxide semiconductor field effect transistor (NDMOSFET).

In one embodiment, the shunt regulators X1, X2, and X3 can be voltage comparators having the same reference voltage, ie, Vref, _X1 = Vref, _X2 = Vref, _X3 = Vref. However, the reference voltages of the shunt regulators X1, X2, and X3 are different, and their reference voltages are respectively added to the terminal voltages of the anode terminals. For example, the reference voltage of the shunt regulator X1 is the sum of the reference voltages of the shunt regulators X1, X2, and X3 and the breakdown voltages of the Zener diodes Zd2 and Zd1, that is, 3Vref+2V z (assuming Zener diodes) The breakdown voltages of the bodies Zd2 and Zd1 are both Vz), and the reference voltage of the shunt regulator X2 is the sum of the reference voltages of the parallel adjustment X2 and X3 and the breakdown voltage of the Zener diode Zd2, that is, 2Vref+V z , parallel adjustment The reference voltage of the device X3 is the reference voltage of the parallel adjustment X3, that is, Vref, _X3 . Of course, in some embodiments, voltage comparators having different reference voltages can also be used as shunt regulators X1, X2, and X3 as needed.

In this embodiment, the bypass switches S10 to S30 are normally closed switches, for example, an N-channel depletion-mode metal oxide semiconductor field effect transistor (NDMOSFET). When the potential difference between the gate and the source is zero or is not subjected to voltage (V _GS ≧0), the potential difference between the gate and the source is to receive a sufficiently negative voltage (V _GS <Vth<0, Vth denotes a transistor) When the cutoff voltage is), the channel is cut off.

In an embodiment, a sinusoidal voltage compensator (eg, series resistors R1 and R2) is selectively provided. First, consider that the value of the resistor R1 is approximately infinite, and the value of the resistor R2 is similar to 0, that is, the case where the resistor R1 is open and the resistor R2 is short-circuited. During the first half of the input voltage, as the input voltage (line voltage) rises, the number of stages of the lit LED sub-array increases. Assuming that the LED sub-array G4 of the last stage is illuminated, the current through the LED sub-array G4 is I1, and the currents of the sub-level two sub-arrays G4 and G3 are illuminated, the current through the LED sub-arrays G4 and G3 is I2, when the rear three-level LED sub-arrays G4, G3, and G2 are all lit, the current through the LED sub-arrays G4, G3, and G2 is I3, and all the LED sub-arrays G4, G3, G2, and G1 are lit, The current of the LED array G is I4 (current I4>current I3>current I2>current I1), and the current is regulated by the current regulator 120 and the switch control circuit to output at a fixed current, current I1, current I2, current I3, and current I4. Presents a sinusoidal (Quasi-sinusoidal wave) step waveform.

The current detecting resistor 160 is disposed in the current loop of the LED array G. Assuming that the weak current input to the comparison circuit is ignored, the current through the LED sub-array will be approximately equivalent to the current through the current sense resistor 160. Therefore, the magnitude of the input current is related to the voltage across the current detecting resistor 160 to correspondingly regulate the turn-on or turn-off of the shunt regulators X1 to X3. The shunt regulators X1~X3 are respectively coupled to the high voltage end of the current detecting resistor 160 through the anti-clamping resistors Rx1~Rx3, and the anti-clamping resistors Rx1~Rx3 are used to avoid the current I _LED passing through the LED sub-array being greater than the current I1 and current. I2 or current I3, respectively, may cause the voltage level of the reference terminal of the shunt regulator X3, X2 or X1 to be clamped at the reference voltage Vref, causing the voltage across the current detecting resistor 160 to be pinned to the reference voltage, thereby suppressing The current through the LED sub-array is rampant.

During the first half of the input voltage, the input voltage gradually rises. When the input voltage overcomes the forward voltage drop V _{G4 of the} LED sub-array _G4 , but has not overcome the forward voltage drop (V _G4 + V _G3 ) of the LED sub-arrays G3 and G4, the current I1 passes through the bypass switch S10~S30 to the LED sub- The array G4 is generated by the current detecting resistor 160 and the voltage across the voltage V ₁₆₀ = I 1 × ( R 160). Assuming that the influence of the anti-clamping resistor Rx3 is ignored, the current detecting resistor 160 is designed to generate a voltage across the voltage V _{160 which is} slightly larger than the parallel adjustment. The reference voltage Vref, _X3 of the device X3 turns on the parallel regulator X3, and the gate potential of the bypass switch S30 is turned off by the parallel regulator X3 through the shunt regulator X3 and is pulled low to the negative level. Then, the input current drops, the shunt regulator X3 is turned off, the bypass switch S30 is turned on again, and the bypass switch S30 is quickly switched between the off state and the on state, and the state is defined as an adjustment state to pass the last stage LED sub-array G4. The current is maintained at current I1.

As the input voltage overcomes the forward voltage (V _G4 +V _G3 ) of the first and second LED sub-arrays G4 and G3, but has not overcome the backwards of the first, second and third LED sub-arrays G4, G3 and G2 the voltage drop _{(V G4 + V G3 + V} G2), the current I2 (I2> I1) switches S10 and S20 by the bypass flow to the LED sub-array G3 and G4, at this time, the voltage across the current detecting resistor of the slightly V _{160 160} The reference voltage Vref, _X2 , which is greater than the shunt regulator _X2 , causes the shunt regulator X2 to quickly switch between on and off. The bypass switch S20 is controlled by the shunt regulator X2 to operate in an adjusted state to maintain the current through the illuminated LED sub-array at current I2. At the same time, the voltage across the voltage detecting resistor 160 V _{160 is} greater than the reference voltage of the shunt regulator X3, so the shunt regulator X3 is always turned on, the bypass switch S30 is always turned off, and the negative potential applied between the gate and the source of the bypass switch S30, It can be approximated by the sum of the forward voltage drop of the last stage LED sub-array G4 and the voltage across the current sense resistor 160 (V _G4 + V ₁₆₀ ) through the resistors Rz3 and Rg3.

When the input voltage is between the forward voltage drop of the last three LED sub-arrays G4, G3, and G2 (V _G4 + V _G3 + V _G2 ) and the forward voltage drop of the last four LED sub-arrays G4, G3, G2, and G1 Between (V _G4 +V _G3 +V _G2 +V _G1 ), the voltage across the voltage detecting resistor 160 V _{160 is} slightly larger than the reference voltage Vref of the shunt regulator X1, _X1 , and the bypass switch S10 enters the regulation state to pass the last stage. The current of the LED sub-array G4 is maintained at current I3. At the same time, the gate potential of the bypass switch S20 is transmitted through the resistors Rz2 and Rg2, and is cut off by the shunt regulator X2 being pulled to the negative level. The negative level can be approximated by the forward voltage drop of the LED sub-arrays G4 and G3. The sum of the voltages across the current detecting resistor 160 (V _G4 + V _G3 + V ₁₆₀ ) is divided by the resistor Rz2 and the resistor Rg2. The gate potential of the bypass switch S10 is transmitted through the resistors Rz1 and Rg1, and is cut off by the shunt regulator X1 being pulled to the negative level. The negative level can be approximated by the forward voltage drop and current of the LED sub-arrays G2 G4. The sum of the voltage across the voltage across the sense resistor (V _G4 + V _G3 + V _G2 + V ₁₆₀ ) is divided by the resistor Rz3 and the resistor Rg3.

And so on, until the input voltage overcomes the forward voltage drop (V _G4 + V _G3 + V _G2 + V _G1 ) of the last four LED sub-arrays G4, G3, G2 and G1, the current regulator 120 provides a constant current I4 to all LED sub-array G1~G4, and current ( Vref , _X is the reference voltage of shunt regulator X). Since the current I4>the current I3>the current I2>the current I1, the current I4 crosses the voltage across the current detecting resistor 160, and the parallel regulators X1, X2, and X3 are inevitably turned on, and the bypass switches S10, S20, and S30 are turned off. At this time, part of the input current is directly supplied from the current regulator 120 to the LED array G, and the input current is charged to the capacitance between the gate and the source of the MOSFET by the starting resistor Ra to turn on the MOSFET. M, the current I4 is supplied to the LED array G through the resistor Rx via the MOS field-effect transistor M. At the same time, the shunt regulator X detects the voltage across the resistor Rx and switches between the off and the on, so that the metal oxide half field effect transistor M operates correspondingly in the regulated state to maintain the current through all the LED sub-arrays G1 G G4 Current I4. The internal circuit of the current regulator 120 is only an illustration, the parallel regulator X can be replaced by a double carrier junction transistor, and the gold oxide half field effect transistor M can be an enhanced or depleted metal oxide half field effect transistor, and is not particularly limited. .

During the second half of the input voltage, the input voltage gradually decreases. After detecting the voltage across the current detecting resistor 160 by the shunt regulator X1, X2 or X3, respectively switching to the on or off voltage compared with the reference voltage of the shunt regulator X1, X2 or X3, controlling the resistor Rz1 and the resistor Rg1, the resistor The circuit of Rz2 and the resistor Rg2, the resistor Rz3 or the resistor Rg3 is formed or not. When the loop is formed, a negative voltage is generated between the gates of the bypass switch S10, S20 or S30 to control the operating state of the bypass switch S10, S20 or S30, and the LED sub-arrays G1, G2, G3 and G4 are extinguished step by step. .

In the embodiment, the Zener diodes Z1, Z2, and Z3 are further disposed between the gate and the source of the bypass switches S10, S20, and S30 (assuming that the breakdown voltages of the Zener diodes Z1, Z2, and Z3 are both For Vz), the bypass switch S10, S20 or S30 and the gate-source voltage can be controlled in the Zener diode The breakdown voltage Vz is applied to protect the insulating layer between the gate and source of the bypass switch S10, S20 or S30 from being broken down.

In summary, the electronic control device of the LED light engine illustrated in FIG. 2A controls the source gate of the current bypass switch by using the sum of the forward voltage drops including the LED sub-array of the current stage and the LED sub-array below the stage. The voltage of the pole is used to adjust the operating state (on, regulated or off state) of the stage bypass switch. As the voltage waveform rises in the first half of the cycle, the line current rises, the LED sub-array lights up step by step, and the current that illuminates the LED sub-array rises. As the voltage waveform falls in the second half of the cycle, the line current decreases, the LED sub-array is extinguished step by step, and the current that illuminates the LED sub-array decreases. Specifically, the shunt regulators X1, X2, and X3 detect the voltage across the current detecting resistor 160 through the anti-clamping resistors Rx1, Rx2, and Rx3, respectively. In the embodiment, it is assumed that the influence of the anti-clamping resistors Rx1, Rx2, and Rx3 is ignored, and when the step shunt regulator is turned on and turned on between the on and off states, the lower shunt regulator must be turned on. In other words, when the stage bypass switch operates in the regulated state, the lower bypass switch must be turned off, thus correspondingly controlling the lighting or extinguishing state of the LED sub-array, and stabilizing the current through the LED sub-array.

Next, consider that the resistor R1 and the resistor R2 are between 0 and infinity (0 < R1 < ∞ and 0 < R2 < ∞). When only the last stage LED sub-array G4 is illuminated, the current passing through is I1. The value of the voltage across the voltage detecting resistor 160 V ₁₆₀ is compensated by the input voltage through the sinusoidal voltage compensator (resistor R1 and resistor R2), ie And the compensation value is a partial pressure of the DC pulse after the input voltage is rectified by the rectifier 100. Therefore, the current through the illuminated LED sub-array is That is, a sinusoidal step waveform such as current I1 that illuminates the LED sub-array is compensated to be closer to the waveform of the sine wave, and thus closer to the waveform of the line voltage. In this way, the power factor and the harmonic distortion can be further improved. Similarly, the current waveform through the illuminated LED sub-arrays G3 and G4, and the current waveform through the illuminated LED sub-arrays G2, G3, and G4, I3 are also subject to the input voltage provided by the sinusoidal voltage compensator. Pressure compensation, respectively And Can further improve the power factor and reduce harmonic distortion.

2B is another schematic circuit diagram of the electronic control unit having the LED light engine in accordance with FIG. 1A. The difference from FIG. 2A is that the comparison circuit controls the on or off of the bypass switch through a pair of carrier junction transistors. The collectors of the dual-carrier junction transistors P1, P2, and P3 are respectively coupled to the cathodes of the LED sub-arrays G2, G3, and G4, so that the source gates of the bypass switches S10, S20, and S30 are applied with a driving. The voltage, the driving voltage is the forward voltage drop of each segment of the LED sub-array, and the voltage division generated by the resistor Rz1 and the resistor Rg1, the resistor Rz2, the resistor Rg2, the resistor Rz3, and the resistor Rg3.

When the input voltage overcomes the forward voltage drop of the last stage LED sub-array G4, but is insufficient to overcome the forward voltage drop of the reciprocal two-stage LED sub-arrays G4 and G3, the current I1 is across the voltage V ₁₆₀ generated by the current detecting resistor ₁₆₀ . The shunt regulator X3 is rapidly switched between the on and off states, so that the pnp bipolar junction transistor (BJT) P3 is switched between on and off, and the bypass switch S30 is rapidly switched to Between the off-state and the on-state, the source gate voltage of the bypass switch S30 is pulled low by the pnp bipolar junction transistor P3 through the resistors Rz3 and Rg3, and the gate of the bypass switch S30 is applied. A sufficient negative voltage is cut off. This negative voltage is similar to the forward voltage of the LED sub-array G4 of the last stage falling below the voltage divider of the resistor Rz3 and the resistor Rg3 ( At this time, the bypass switch S30 operates in an adjusted state to maintain the current through the last stage LED sub-array G4 at the current I1.

When the input voltage overcomes the forward voltage drop of the last two LED sub-arrays G4 and G3, but is insufficient to overcome the forward voltage drop of the last three LED sub-arrays G4, G3, and G2, the current I2 is generated by the current detecting resistor 160. The voltage across the voltage V _{160 is} such that the shunt regulator X2 is rapidly switched between the on and off states, and the pnp bipolar junction transistor P2 is switched between on and off, when the pnp bipolar junction transistor P2 is turned on. The source gate voltage of the bypass switch S20 is pulled down by the pnp bipolar junction transistor P2 through the resistors Rz2 and Rg2, and the gate of the bypass switch S20 is applied with a sufficient negative voltage to cut off, and the negative voltage is approximated. The forward voltage of the LED sub-array G3 in the penultimate stage is reduced by the voltage division of the resistors Rz2 and Rg2 ( The bypass switch S20 is switched to the off and on, at which time the bypass switch S20 operates in the regulated state to maintain the current through the last secondary LED sub-arrays G4 and G3 at the current I2. At the same time, the shunt regulator X3 is constantly turned on, and the bypass switch S30 operates in the off state.

When the input voltage overcomes the forward voltage drop of the last three LED sub-arrays G4, G3, and G2, but is insufficient to overcome the forward voltage drop of the last four LED sub-arrays G4, G3, G2, and G1, the current I3 is current-detected. ₁₆₀ V voltage across resistor 160 generated by the shunt regulator X1 to quickly switch between oN and oFF states, PNP bipolar junction transistor P1 is switched on and off conduction between. When the pnp bipolar junction transistor P1 is turned on, the source gate voltage of the bypass switch S10 is turned off by the pnp bipolar junction transistor P1 to a sufficient negative voltage through the resistors Rz1 and Rg1, and the negative is turned off. The forward voltage of the LED sub-array G2 with a voltage approximating to the third last stage is reduced by the voltage division of the resistors Rz1 and Rg1 ( ). The bypass switch S10 is switched to off and on to operate in an adjusted state to maintain the current through the last three stages of LED sub-arrays G4, G3, and G2 at current I3. At the same time, the shunt regulators X2 and X3 are turned on, and the bypass switches S20 and S30 are operated in the off state. By analogy, the current regulator 120 provides a constant current I4 to all of the LED sub-arrays G1 - G4 until the input voltage overcomes the forward voltage drop across all of the LED sub-arrays.

In summary, the electronic control device of the LED light engine illustrated in FIG. 2B utilizes the forward voltage drop of the next-level LED sub-array to control the source gate voltage of the current-stage bypass switch, thereby adjusting the level bypass switch of the stage. The operating state (on, regulated, or off state), thereby correspondingly controlling the lighting or extinguishing state of the LED sub-array, and stabilizing the current through the LED sub-array. The lighting mechanism and dimming mechanism of the LED sub-array are similar to those of FIG. 2A and will not be described herein. Assume that the effects of the anti-clamping resistors Rx1, Rx2, and Rx3 are ignored. When the stage bypass switch operates in the regulation state, the lower-level bypass switch must be turned off, thus correspondingly controlling the lighting or extinguishing state of the LED sub-array, and stably passing The current of the LED sub-array.

FIG. 3A is a schematic diagram showing another specific circuit of the electronic control unit having the LED light engine according to FIG. 1A. The difference from FIG. 2A is that the shunt regulators X1, X2, and X3 are replaced by bipolar junction transistors B1, B2, and B3. The base of the bipolar junction transistor B1 is coupled to the anti-clamping resistor Rx1, and the base of the bipolar junction transistor B2 is coupled to the anti-clamping resistor Rx2, the bipolar junction transistor The base of B3 is coupled to the anti-clamping resistor Rx3.

The roles of the bi-carrier junction transistors B1, B2, and B3 of Figure 3A are similar to the shunt regulators X1, X2, and X3 of Figure 2A. The difference is that the shunt regulator compares the voltage received by the reference terminal (relative to the ground terminal voltage) with its reference voltage (the sum of the reference terminal-to-anode reference voltage and its anode-to-ground voltage) to control the conduction or the cut-off of the shunt regulator. . The bi-carrier junction transistor controls the bi-carrier junction by comparing the voltage received by the base (relative to the ground voltage) with its reference voltage (the sum of the emitter-to-electrode threshold voltage and the emitter-to-ground voltage). The transistor is turned on or off.

For example, when the input voltage overcomes the forward voltage drop of the last stage LED sub-array G4, but is insufficient to overcome the forward voltage drop of the inverse two-stage LED sub-arrays G4 and G3, the current I1 is generated by the current detecting resistor 160. The voltage V _{160 is} such that the bipolar junction transistor B3 is rapidly switched between the on and off states. The bypass switch S30 is quickly switched to off and on by the control of the bipolar junction transistor B3. It is defined that the bypass switch S30 is operated in the regulation state to maintain the current through the LED sub-array G4 at the current I1.

By analogy, when the input voltage is between the forward voltage drop of the LED sub-array of the last three stages (G2~G4) to the last four stages (G1~G4), the current I3 is generated by the current detecting resistor 160. V ₁₆₀ causes the bipolar junction transistor B1 to rapidly switch on and off, causing the bypass switch S10 to operate in an regulated state to maintain the current through the LED sub-arrays G2, G3, G4 at current I3. ₁₆₀ V voltage across the current I3 through the current detection resistor 160 generated will make bipolar junction transistors B2 and B3 constant on, constant bypass switches S30 and S20 are turned off. Until the input voltage overcomes the forward voltage drop across all of the LED sub-arrays, current regulator 120 provides a constant current I4 to illuminate all of the LED sub-arrays G1 - G4.

On the contrary, in the falling edge of the half cycle of the input voltage, as the voltage drops, the bypass switches S10, S20 and S30 are controlled by the bipolar junction transistors B1, B2 and B3, respectively, and are turned on step by step, so that the LEDs are turned on. The arrays G1, G2, G3, and G4 are extinguished step by step. In addition, the sinusoidal voltage compensator (resistor R1 and resistor R2) is used to extract the waveform of the line voltage of the input power source, so that the principle of modifying the line current waveform has been described above, and will not be described again.

FIG. 3B is a schematic diagram showing another specific circuit of the electronic control unit having the LED light engine according to FIG. 1A. The difference from FIG. 2B is that the shunt regulators X1, X2, and X3 are replaced by bipolar junction transistors B1, B2, and B3. The roles of the bi-carrier junction transistors B1, B2, and B3 are similar to those of FIG. 3A, and the mechanism of action has been described above and will not be described again.

In one embodiment of the invention, the current through the LED sub-array can be adjusted by adjusting the current through the current sense resistor 160 to adjust the brightness of the LED sub-array. 4A-4D illustrate an electronic control device for the LED light engine of FIG. 1A for illustrating a dimming strategy of an embodiment having a dimming function. In some embodiments, the shared current sensing and modulation units 160a-160d of FIGS. 4A-4D are several specific forms of the current detecting resistor 160 of FIGS. 1A-1B, by The currents of the current sensing and modulation units 160a-160d approximate the current of the lit LED array, and the resistance of the shared current sensing and modulation units 160a-160d can be adjusted to regulate the current of the lit LED array. To control the brightness of the illuminated LED sub-array. The shared current sensing and modulation unit 160a-160d can be applied to any embodiment of the present invention, instead of the block diagram of the current detecting resistor 160, so that the current through the LED array is approximated by the shared current sensing and modulation unit 160a~ 160d to provide an electronic control unit for the LED light engine that simplifies the dimming mechanism.

Referring to FIG. 4A firstly, the shared current sensing and modulation unit 160a includes a voltage controlled resistance of the transistor, including a Pulse Width Modulation (PWM) unit PWM, a resistor R15, and a resistor. R16, voltage dividing resistors Rm1 and Rm2, capacitor Cf, gold oxide half field effect transistor (MOSFET) M16 and voltage follower F (Voltage Follower) F. The pulse width modulation unit PWM can provide a pulse width modulation signal, and transmits the microwave through a Bluetooth function of a remote control device (such as a mobile phone, a remote controller, etc.), for example, a transmitter (Transmitter) provided with an antenna in the remote control device, and the illumination device A receiver (Receiver) is provided in the circuit architecture, and the pulse signal is transmitted by the transmission of the remote control device and the reception of the illumination device. Alternatively, the pulse width modulation can also be generated by a built-in signal generator.

In the state where the frequency is constant, the overall average voltage value of the signal can be adjusted to rise or fall by adjusting the duty cycle of the pulse width modulation signal. Then, through the antenna transmission or built-in pulse width modulation signal, through the low-pass filter composed of the resistor R16 and the capacitor Cf, the analog signal is outputted to the voltage follower F to transfer the analog signal to the gold. Oxygen half field effect transistor M16. The voltage follower F ensures that the analog signal transmission is not distorted, does not draw current itself, and provides sufficient current to drive the metal oxide half field effect transistor M16 without causing a load effect on the circuit.

The gold-oxygen half-field effect transistor M16 is used as a voltage-controlled resistor, and the analog signal provided by the voltage dividing resistors Rm1 and Rm2 is received between the gate and the source to form a channel between the drain and the source, and a corresponding discharge is generated. A large current, this amplified current is inversely proportional to the resistance of the metal oxide half field effect transistor M16. That is, the resistance of the metal oxide half field effect transistor M16 can be regulated, and the current through the metal oxide half field effect transistor M16 is about the current through the LED sub-array. Therefore, by adjusting the duty cycle of the pulse width modulation signal, the overall average voltage value of the signal can be adjusted to control the resistance of the metal oxide half field effect transistor M16, and the current through the gold oxide half field effect transistor M16 can be modulated (approximate In the current through the LED sub-array, as such, the current through the LED sub-array can be controlled to adjust the illumination brightness. In the above embodiments, other voltage-controlled resistors such as a junction field effect transistor (JFET) may be used instead of the gold-oxygen half-field effect transistor, and the working principle is similar, so it is not described here.

Referring to FIG. 4B, the shared current sensing and modulation unit 160b includes a transistor as a switch, including a pulse width modulation unit PWM, a resistor R15, a resistor Rp, and a bipolar junction transistor (BJT) B16. In this embodiment, the signal of the pulse width modulation unit PWM is provided as a current signal through the resistor Rp to provide the base of the bipolar junction transistor (BJT) B16, thereby modulating the bipolar junction transistor B16. Turn on or off to regulate the average current through the LED sub-array. In this way, the brightness of each segment of the LED sub-array can be adjusted.

Referring to FIG. 4C, the shared current sensing and modulation unit 160c includes a transistor as a switch, including a pulse width modulation unit PWM, a resistor R15, voltage dividing resistors Rm1 and Rm2, and a gold oxide half field effect transistor M16. In this embodiment, the signal of the pulse width modulation unit PWM is supplied to the gate source of the gold-oxygen half-field transistor M16 as a voltage signal through a voltage dividing resistor Rm1 and Rm2 to modulate the gold-oxygen half-field effect transistor M16. Turning on or off, controlling the average current through the LED sub-array to control the brightness of each segment of the LED sub-array.

Referring next to FIG. 4D, the shared current sensing and modulation unit 160d is a potentiometer (ie, a variable resistor). By adjusting the resistance of the potentiometer, the current through the potentiometer is controlled to regulate the current through the LED sub-array to adjust the illumination brightness.

In summary, the dimming mechanism of the above embodiment of the present invention assumes that the current flowing through the shared current sensing and modulation unit 160a-160d can be approximated to be illuminated until the current flowing to the bypass switches S1 S S3 is ignored. The current of the LED sub-array controls the brightness of the illuminated LED sub-array by modulating the current through the shared current sensing and modulation units 160a-160d. Moreover, as the voltage waveform rises in the first half of the cycle, the line current rises, the LED sub-array lights up step by step, and the current that illuminates the LED sub-array rises. As the voltage waveform falls in the second half of the cycle, the line current decreases, the LED sub-array is extinguished step by step, and the current that illuminates the LED sub-array decreases.

FIG. 5A is a schematic diagram showing another specific circuit of the electronic control unit having the LED light engine according to FIG. 1A. The difference from FIG. 2A is that the bypass switches S15, S25, and S35 of the embodiment include a metal-oxide-semiconductor FET (MOSFET), which is an enhanced type, that is, a bypass switch S15. S25 and S35 are normally open switches. When no voltage is applied to the gate source or the applied voltage is less than the threshold voltage, the bypass switch is turned off. When the voltage applied to the gate source is greater than or equal to the threshold value. When the voltage is applied, the bypass switch is turned on.

The bypass switches S15, S25 and S35 are normally open switches, and the initial state needs to be established first, so that the bypass switches S15, S25 and S35 are turned on. In the embodiment, the starting resistors Ra1 to Ra3 are respectively disposed between the gates and the drains of the bypass switches S15, S25, and S35. In the first half of the cycle of the input voltage (rising edge), when the input voltage overcomes the forward voltage drop of the last stage LED sub-array, the first stage of the starting resistor Ra1 can draw the input voltage to the gate of the bypass switch S15, The capacitor (not shown) between the gate and the source of the bypass switch S15 is charged, so that the bypass switch S15 is turned on, and the current flows to the drain of the bypass switch S25 through the source of the bypass switch S15, and the second stage The starting resistor Ra2 connected to the drain of the bypass switch S25 then charges the capacitance between the gate and the source of the bypass switch S25, so that the bypass switch S25 is turned on. In this way, until the last stage of the bypass switch S35 is turned on and enters the regulation state to regulate the current at the current I1, the current I1 flows through the bypass switches S15, S25 and S35 The last stage LED sub-array G4 is finally passed to the current detecting resistor 160. The detailed mechanism for illuminating the LED sub-array has been described above and will not be described again.

In the second half of the cycle of the input voltage (falling edge), when the input voltage drops insufficient to overcome the forward voltage drop of all LED arrays, it still overcomes the forward voltage drop of the third-order LED sub-arrays G4, G3, and G2. (V _G4 +V _G3 +V _G2 ), the voltage across the voltage detecting resistor 160 V ₁₆₀ turns on the parallel regulator X1, and the source voltage of the bypass switch S15 is pulled low through the circuit of the diode D1 and the resistor Rd1, so that the side The switch S15 is turned off. When the input voltage drops insufficient to overcome the forward voltage drop of the third-order LED sub-arrays G4, G3, and G2 (V _G4 +V _G3 +V _G2 ), but overcomes the forward direction of the final two-level LED sub-arrays G4 and G3 When the voltage drops (V _G4 +V _G3 ), the voltage across the voltage V _{160 of} the current detecting resistor 160 turns on the parallel regulator X2, and the source voltage of the bypass switch S25 is pulled low through the circuit of the diode D2 and the resistor Rd2, so that The switch S25 is turned off, and so on, to extinguish the LED sub-array step by step. The mechanism for extinguishing the LED sub-array has been described before and will not be described again.

FIG. 5B is a schematic diagram showing another specific circuit of the electronic control unit having the LED light engine according to FIG. 1A. This embodiment is not described in detail in the same manner as in FIG. 5A. The difference is that the operating states of the enhanced bypass switches S15, S25, and S35 are controlled by the conduction of the dual-carrier junction transistors P4, P5, and P6. . In FIG. 5B, when the normally open switches of the bypass switches S15, S25 and S35 are subjected to the initial state of the input voltage via the starting resistors Ra1 to Ra3, the bypass switches S15 and S25 enter the conducting state and the bypass switch S35 is in the regulated state. . This is the lighting mode of the last stage LED sub-array G4. In this way, the LED sub-array can be illuminated step by step as the input voltage rises.

In the second half of the cycle of the input voltage (falling edge), when the input voltage drops insufficient to overcome the forward voltage drop of all LED arrays, it still overcomes the forward voltage of the third-order LED sub-arrays G4, G3, and G2. Drop (V _G4 +V _G3 +V _G2 ), the voltage across the voltage detecting resistor 160 V ₁₆₀ turns on the parallel regulator X1, the double carrier junction transistor P4 is turned on, and the gate voltage of the bypass switch S15 is pulled low ( Pulled low), the bypass switch S15 is turned off. When the input voltage drops insufficient to overcome the forward voltage drop of the third-order LED sub-arrays G4, G3, and G2 (V _G4 +V _G3 +V _G2 ), but overcomes the forward direction of the final two-level LED sub-arrays G4 and G3 When the voltage drops (V _G4 + V _G3 ), the voltage across the voltage V _{160 of} the current detecting resistor 160 turns on the parallel regulator X2, the bipolar junction transistor P2 is turned on, and the gate voltage of the bypass switch S25 is pulled low. The switch S25 is turned off, and so on, to extinguish the LED sub-array step by step.

6A and 6B are schematic views of different embodiments of an electronic control unit having an LED light engine in accordance with FIG. 1A. The difference between the embodiment of Figures 6A and 6B and Figures 5A and 5B is that the parallel regulators X1, X2 and X3 are replaced by bi-carrier junction transistors B1, B2 and B3. 6A uses, for example, the npn-type bipolar junction transistors B1, B2, and B3 to turn on or off, respectively, to control the circuit of the diode D1 and the resistor Rd1, the circuit of the diode D2 and the resistor Rd2, and the diode. The formation of the loop of the body D3 and the resistor Rd3 controls the turn-off or conduction of the bypass switch. In FIG. 6B, the on or off of the bipolar junction transistors B1, B2, and B3 are controlled to respectively turn on or off the bipolar junction transistors P4, P5, and P6, for example, to control the bypass switch. The cutoff or conduction of S15, S25 and S35.

7A and 7B are schematic diagrams showing a specific circuit of an electronic control unit having an LED light engine in accordance with FIG. 1A. The difference between FIG. 5A and FIG. 5B is that the electronic control device of the LED light engine further includes a voltage regulator array, which is applicable to the circuit structure of any of the foregoing embodiments, and includes a plurality of voltage regulating circuits 180, 182 and 184, respectively. In order to stabilize the on state of the bypass switches S15, S25 and S35. The voltage regulating circuits 180, 182, and 184 illustrated in Figures 7A and 7B are applicable to any of the embodiments of the present invention.

The voltage regulator 180 is taken as an example, and includes a resistor Rv1, a Zener diode Z4, a bipolar junction transistor B7, and a capacitor C1. When the input voltage is rectified by the rectifier 100, it is output through the current regulator 120, supplied to the collector of the bipolar junction transistor B7, and passed through the resistor Rv1 to the Zener diode Z4 to maintain the voltage at the Zener voltage V. _Z4 . At this time, coupled to the voltage V _C1 across the bipolar junction transistor of extremely B7 emitted capacitor C1, is equal to the inter-electrode potential difference V _BE VZ4 base-emitter voltage of the Zener bipolar junction transistor of _{B10, 10} The difference (ie V _C1 =V _Z4 -V _BE,10 ). The voltage regulator 182 and the voltage regulator 184 are similar to the voltage regulator 180 and will not be described again. By means of the voltage regulators 180, 182 and 184, a constant voltage V _C can be supplied via the resistors Ra1 to Ra3 to the gates of the enhanced bypass switches S15, S25 and S35 to charge the capacitance between the gate and the source to establish a bypass. The initial state of the channel formed by the switches S15 to S35. In this way, the bypass switches S15, S25, and S35 can be stably maintained even at the falling edge of the period of the input voltage.

8A-8G are schematic diagrams showing the electronic control device of the LED light engine of FIG. 1A, including a different line regulation tightener. 9A is an electronic control device of the LED light engine according to FIG. 1A and FIG. 8A, 8B or 8B, before and after the line voltage adjustment rate compactor is set, the effective value of the input voltage (v _IN ) thereof, through the LED sub-array A comparison of the current (I _LED ) versus the time axis (t). Parts (a), (b) and (c) of Fig. 9A respectively show waveform comparison diagrams of the effective values of the input voltages at 105V, 120V, and 135V before the line voltage adjustment rate tightener is set, and FIG. 9A(d). The (e) and (f) parts respectively show waveform comparison diagrams when the effective value of the input voltage is 105V, 120V, and 135V after the line voltage adjustment rate is set.

In general, the rms value of the input voltage after rectification can be designed to be 120 volts (V) ± 15V, of which ± 15V is an allowable error range. During the one-week period, the current I _LED of the LED sub-array is divided by the integral of time ( t ₀ ~ t _T ) by one cycle time ( t _T - t ₀ ) as the average current Iave ( t ₀ is the cycle start point, t _T For the end of the cycle, this average current Iave is positively correlated with the rms value of the input voltage. Please refer to FIG. 9A first. Before the line voltage regulation rate tightener is set, if the effective value of the input voltage of part (b) is 120V, then the effective value of the input voltage is small in part (a) ( 105V), the integrated area of I _LED and time is smaller, the average current is smaller, the LED sub-array is darker, and in part (c), the effective value of input voltage is larger (135V), I _LED and time The integrated area is larger, the average current is also larger, and the illuminated LED sub-array is brighter. As a result, within the error range of the effective value of the input voltage, the average current Iave passing through the LED sub-array changes accordingly, so that the brightness of the lit LED sub-array also fluctuates with the error value.

8A-8G illustrate various line voltage regulation rate reducers 140a-140c, 145a, and 148a for stabilizing the average current I _LED passing through the LED sub-array within an allowable range to ensure illumination of the LED sub-array. The brightness does not vary greatly with the variation of the effective value of the input voltage. For example, if the rms input voltage RMS falls within the allowable range V _{IN, NOM} ±15V (V _{IN, NOM} is the nominal voltage, ±15V is the voltage tolerance), and the line voltage regulation rate is set after the tightener is set So that the average current through the LED sub-array falls within the allowable range I _{LED, NOM} ± 5% (I _{LED, NOM} is the nominal current, ± 5% is the current tolerance), then the LED light engine can be called The allowable AC input voltage has a valid value range of V _{IN and NOM} ±15V, and has a line voltage regulation of ±5%. In other words, under the action of such a line voltage regulation rate reducer, as long as the RMS input voltage RMS falls within the allowable range V _{IN, NOM} ±15V, the average current through the LED sub-array will be adjusted. Allowable I _{LED, NOM} ± 5% range.

Referring to FIG. 8A, the current regulator 120 is coupled to the line voltage regulation rate reducer 140a, including the metal oxide half field effect transistor Me, the resistor Re1, the resistor Re2, the resistor Re3, and the resistor Re4 (the resistor Re3 and the resistor Re4 are voltage detectors). Measuring voltage divider resistors, Zener diode Ze and parallel regulator Xe (or dual carrier transistor) for voltage detection. The gate of the gold-oxygen half-field effect transistor Me is coupled to the current regulator 120 through a resistor Re1, and the gate of the metal oxide half field effect transistor Me is coupled to the current regulator 120 through the resistor Re2, the Zener diode Ze and The shunt regulator Xe is coupled between the gate and the source of the gold-oxygen half field effect transistor Me, and a resistor Re4 is disposed between the reference pole of the shunt regulator Xe and the anode.

Please refer to FIGS. 8A and 9A, the cross voltage V is assumed to ignore a sinusoidal voltage compensator ₁₆₀ (R1 and R2) and a current detecting resistor 160 at both ends. When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), and When (the Vth _Xe is the threshold voltage of the shunt regulator Xe), the shunt regulator Xe is turned off, and the starting resistor Re2 provides the gate potential of the gold-oxygen half-field transistor Me to be turned on. At this time, the resistor Rx is connected in parallel with the Re1. (The resistance is Rx∥Re1), the current through the LED sub-array rises from I3 to (corresponding to time t4) of parts (d), (e) and (f) of Fig. 9A, Vth _X is defined as the threshold voltage of the parallel regulator _X in the current regulator 120, and the parallel regulator X detects the parallel resistance Rx. resistance Re1 and operate the regulating state, so mosfet transistor M corresponds to the adjustment operating mode, to stabilize the current I4 ^H. As the input voltage vi continues to rise to overcome the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), and When the shunt regulator Xe is turned on, the gate potential of the metal oxide half field effect transistor Me is pulled off and turned off. At this time, the resistance of the resistor Rx is higher than the resistance value Rx∥Re1, and the current through the LED sub-array is controlled by I4. ^H falls to I4 ^L (corresponding to time t4' of the portion of parts (e), (f) and (g) of Fig. 9A). At this time, the shunt regulator X operates in the regulated state, and the gold-oxygen half-field effect transistor M operates correspondingly in the regulated state, and the current through the LED sub-array is stably maintained. Until the input voltage begins to drop to When the shunt regulator Xe is turned off again, the gold-oxygen half-field effect transistor Me is turned on, the resistor Rx is connected in parallel with Re1 (the resistance of Rx∥Re1 is less than Rx), and the current through the LED sub-array rises from I4 ^L to I4 ^H (time t5) '), the current through the LED sub-array is stable at I4 ^H until the input voltage vi continues to fall and cannot overcome the forward voltage drop of all LED sub-arrays (vi < V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), the current through the LED sub-array drops from I4 ^H to I3 (time t5).

Referring to FIG. 8B, the gate of the metal oxide half field effect transistor M of the current regulator 120 is coupled to the diode Dx, and the gate of the gold oxide half field effect transistor M is coupled to the voltage regulation rate reducer 140b. The line voltage adjustment rate reducer 140b includes a gold oxide half field effect transistor Mf1, a gold oxide half field effect transistor Mf2, a bipolar junction transistor Bf, a resistor Rf1, a resistor Rf2, a resistor Rf3, a resistor Rf4, a resistor Rf5, and a resistor Rf6. Resistor Rf7 (resistance Rf6 and resistor Rf7 are voltage detection sub-piezoelectric Resistor), resistor Rf8, Zener diode Zf1, Zener diode Zf2 and shunt regulator Xf (or bipolar transistor) for voltage detection.

Please refer to FIG. 8B and FIG. 9A simultaneously, assuming that the sinusoidal voltage compensators (R1 and R2) are ignored. When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), and When ( Vth _Xf is defined as the threshold voltage of the shunt regulator Xf), the shunt regulator Xf is turned off, and the starting resistor Rf5 provides the gate potential of the gold-oxygen half-field effect transistor Mf2 to be turned on. At this time, the gold-oxygen half-field electric power The crystal Mf1 is cut off, and the voltage Vbe1 between the base and the emitter of the bipolar junction transistor Bf is Vbe 1, _Bf is the voltage across the voltage detecting resistor 160 V ₁₆₀ is divided by the series resistors Rf1 and Rf2 and the resistor Rf3 The designing of this partial voltage is not sufficient to turn on the bi-carrier junction transistor Bf. Therefore, the loop of the diode Dx cannot be formed, the current through the LED sub-array is regulated by the current regulator 120 (the current is planned by the resistor Rx), and the current through the LED sub-array rises from I3 to (corresponding to time t4) of parts of parts (d), (e) and (f) of Fig. 9A.

As the input voltage vi continues to rise to overcome the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), The shunt regulator Xf is turned on, and the gate potential of the metal oxide half field effect transistor Mf2 is pulled off and turned off, and the metal oxide half field effect transistor Mf1 (voltage detection bypass switch) is turned on to bypass the resistor Rf2, At this time, the voltage Vbe 2, _Bf received between the base and the emitter of the bipolar junction transistor Bf is the voltage division across the voltage V ₁₆₀ of the current detecting resistor ₁₆₀ through the series resistor Rf1 and the resistor Rf3. The voltage can turn on the bipolar junction transistor Bf, so that the gold oxide half field effect transistor M is turned off, the input current is decreased, and the bipolar junction transistor Bf is turned off. The bipolar junction transistor Bf is switched between the on and off states so as to operate in the regulated state, so that the gold oxide half field effect transistor M is switched between the off and the on and operates in the regulated state, and the current through the LED sub-array is I4 ^H drops (corresponding to time t4' of the portion of parts (a), (e) and (f) of Fig. 9), Vbe and _Bf are defined as the threshold voltage of the bipolar junction transistor Bf. The current through the LED sub-array is maintained at I4 ^L such that the voltage across resistor Rx is insufficient to turn on shunt regulator X, and the current is regulated by line voltage regulation rate reducer 140b (current is planned by resistor Rf3) until the input voltage begins to drop. to When the shunt regulator Xf is turned off again, the gold-oxygen half-field effect transistor Mf2 is turned on, the gold-oxygen half-field effect transistor Mf1 is turned off, and the current through the LED sub-array rises from I4 ^L to I4 ^H (time t5') through the LED sub-array. The current is stable at I4 ^H until the input voltage vi continues to fall and cannot overcome the forward voltage drop of all LED sub-arrays (vi < V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), through the LED The current of the array drops from I4 ^H to I3 (time t5).

Referring to FIG. 8C, the gate of the gold-oxygen half-effect transistor M of the current regulator 120 is coupled to the diode Dx, and the gate of the gold-oxygen half-effect transistor M is coupled to the voltage regulation rate reducer 140c. The line voltage adjustment rate reducer 140c includes a photocoupler element Pf, a bipolar junction transistor Bh, a resistor Rt1, a resistor Rt2, a resistor Rt3, a resistor Rt4, a resistor Rt5, and a resistor Rt6 (the resistor Rt5 and the resistor Rt6 are voltage detection points). Voltage resistor), resistor Rt7 and shunt regulator Xh (or bipolar transistor) for voltage detection. The photocoupler element Pf includes a photodiode Dp and a phototransistor Bp (voltage detection bypass switch), and an anode of the photodiode Dp is coupled to the voltage source Vcc. When the photodiode Dp is turned on, it emits light, so that the photo-electric crystal Bp can be turned on.

Please refer to FIG. 8C and FIG. 9A simultaneously, assuming that the sinusoidal voltage compensators (R1 and R2) are ignored. When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), and When ( Vth _Xh is defined as the threshold voltage of the shunt regulator Xh), the shunt regulator Xh is turned off, the photodiode Dp has no loop, the photonic crystal Bp is turned off, and the base and emitter of the bipolar junction transistor Bh are The received voltages Vbe 1, _Bh are the voltage across the voltage detecting resistor 160 V ₁₆₀ , and the voltage division of the series resistors Rt1 and Rt2 and the resistor Rt3 is designed to be insufficient to turn on the bipolar junction transistor Bh. Therefore, the loop of the diode Dx cannot be formed, the current through the LED sub-array is regulated by the current regulator 120 (the current is planned by the resistor Rx), and the current through the LED sub-array rises from I3 to (corresponding to time t4) of parts of parts (d), (e) and (f) of Fig. 9A.

As the input voltage vi continues to rise to overcome the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), The shunt regulator Xh is turned on, the photodiode Dp is turned on, and the photo transistor Bp is turned on to bypass the resistor Rt2. At this time, the voltage Vbe 2, _Bh received between the base and the emitter of the bipolar junction transistor Bh is the voltage division across the voltage V ₁₆₀ of the current detecting resistor ₁₆₀ through the series resistor Rt1 and the resistor Rt3. The voltage can make the bi-carrier junction transistor Bh turn on, so that the gold-oxygen half-field effect transistor M is turned off, the input current decreases, and the bi-carrier junction transistor Bh is turned off. A bipolar junction transistor operating in Bh adjustment state so that metal oxide semiconductor field effect transistor M corresponds to the adjustment operating mode, current is reduced by the I4 ^H (corresponding to time t4' of the portion of parts (a), (e) and (f) of Fig. 9), Vbe and _Bh are defined as the threshold voltage of the bipolar junction transistor Bh. The current through the LED sub-array is maintained at I4 ^L (where current I4 ^H >I4 ^L >I3), so that the voltage across resistor Rx is insufficient to conduct shunt regulator X, and the current is primarily regulated by line voltage regulation rate reducer 140c ( The current is planned by the resistor Rt3). When the input voltage drops to When the shunt regulator Xh is turned off again, the phototransistor Bp is turned off, the bipolar junction transistor Bh is turned off, the current through the LED sub-array is raised from I4 ^L to I4 ^H (time t5'), and the current through the LED sub-array is current regulator 120 stabilize I4 ^H, until the input voltage vi continues to fall can not overcome the forward voltage drop of all the LED sub-array _{(vi <V G 1 + V} G 2 + V G 3 + V G 4 = V G), by The current of the LED sub-array drops from I4 ^H to I3 (time t5).

In summary, in the embodiment of FIGS. 8A-8C and FIG. 9A, after the current voltage adjustment rate reducer 140a, 140b or 140c is set by the current I0~I3 of the LED sub-array ((d), (e of FIG. 9A) The waveforms of the parts (f) and (f) are substantially the same as those before the line voltage adjustment rate tighteners 140a, 140b or 140c are disposed (the waveforms of parts (a), (b) and (c) of Fig. 9A). The setting of the line voltage regulation rate reducer 140a, 140b or 140c is mainly to change the input voltage to overcome the forward voltage drop of all the LED sub-arrays, and divide the current I4 through the LED sub-array into I4 ^H and I4 ^L , and I4=I4 ^H >I4 ^L >I4>I3>I2>I1. The higher the effective value of the input voltage vi, the larger the slope of the rising edge and the falling edge of the waveform of the input voltage vi, indicating the time t4 to t4' elapsed by the current I4 ^H passing through the LED sub-array. The shorter, the longer the interval t4' to t5' of the current I4 ^L passing through the LED sub-array. Therefore, the integrated area of the current I _LED and the time passing through the LED sub-array can be adjusted to stabilize the average current without being affected by the effective value of the input voltage vi.

Please refer to the circuit diagrams of FIG. 8D-8G and the waveform diagram of FIG. 9B. The LED light engine electronic control device of FIG. 8D-8G changes the line voltage adjustment rate compactor according to the architecture of the LED light engine electronic control device of FIG. 8A. Implementation architecture. Of course, the implementation architecture of the line voltage regulation rate reducer of Figures 8D-8G can also be applied to the architecture of the LED light engine electronic control unit of Figure 8B or 8C.

Referring to FIG. 8D, the current regulator 120 is coupled to a first line voltage regulation rate reducer 140a and a second line voltage regulation rate tightener 145a. The first line voltage regulation rate reducer 140a includes a metal oxide half field effect transistor Me, a resistor Re1, a resistor Re2, a resistor Re3, a resistor Re4 (the resistor Re3 and the resistor Re4 are voltage detecting voltage dividing resistors), and a Zener diode Ze And parallel regulator Xe (or dual carrier transistor) as voltage detection. The second line voltage regulation rate reducer 140b includes a gold oxide half field effect transistor Mj, a resistor Rj1, a resistor Rj2, a resistor Rj3, a resistor Rj4 (the resistor Rj3 and the resistor Rj4 are voltage detecting voltage dividing resistors), and a Zener diode Zj. And parallel regulator Xj (or dual carrier transistor) as voltage detection. The drain of the gold-oxygen half-field effect transistor Mj is coupled to the current regulator 120 through a resistor Rj1, and the gate of the gold-oxygen half-field effect transistor Mj is coupled to the current regulator through the resistor Rj2. 120, the Zener diode Zj and the shunt regulator Xj are coupled between the gate and the source of the gold-oxygen half field effect transistor Mj, and a resistor Rj4 is disposed between the reference pole and the anode of the shunt regulator Xj.

Please refer to FIG. 8D and FIG. 9B simultaneously, assuming that the sinusoidal voltage compensators (R1 and R2) are ignored. When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), And (Defining Vth _Xe is the threshold voltage of shunt regulator Xe, Vth _Xj is the threshold voltage of shunt regulator Xj, where Vth _Xe and Vth _Xj may be the same or similar, and At this time, the shunt regulator Xe is turned off, the starting resistor Re2 provides the gate potential of the metal oxide half field effect transistor Me to be turned on, and the shunt regulator Xj is turned off, and the starting resistor Rj2 provides the gold oxide half field effect transistor Mj. The gate potential is turned on. At this time, the resistor Rx is connected in parallel with Re1 and Rj1 (the resistance is Rx∥Re1∥Rj1), and the current through the LED sub-array rises from I3 to (corresponding to time t4) of parts (d), (e) and (f) of Fig. 9B, it is defined that Vth _X is the threshold voltage of the parallel regulator _X in the current regulator 120, and the parallel regulator X detects the parallel resistance. Rx, Re1 and Rj1 resistance state is adjusted to operate the metal oxide semiconductor field effect transistor M corresponds to the adjustment operating mode, to stabilize the current I4 ^H.

When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), And ( Vth _Xe is the threshold voltage of the shunt regulator Xe, Vth _Xj is the threshold voltage of the shunt regulator Xj). At this time, the shunt regulator Xe is turned off, and the starting resistor Re2 provides the gate potential of the metal oxide half field effect transistor Me. And make it conductive. Moreover, the shunt regulator Xj is turned on, and the gate potential of the gold-oxygen half-field effect transistor Mj is pulled off and turned off. In this case, Re1 in parallel with the resistor Rx (resistance to Rx∥Re1), down to the current through the LED array by the sub-I4 ^H (corresponding to time t4 _{1 of} part (d), (e) and (f) of Fig. 9B, Vth _X is defined as the threshold voltage of the parallel regulator _X in the current regulator 120, and the parallel regulator X detects the parallel connection. The resistances of the resistors Rx and Re1 are operated in the regulated state, so that the gold-oxygen half-effect transistor M operates correspondingly in the regulated state to stabilize the current at I4 ^M .

As the input voltage vi continues to rise to overcome the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), and but When the parallel regulators Xe and Xj are both turned on, the gate potentials of the metal oxide half field effect transistors Me and Mj are pulled off and turned off. At this time, the resistance of the resistor Rx is higher than the resistance value Rx∥Re1, and the current through the LED sub-array is reduced from I4 ^M to I4 ^L (corresponding to the time of the parts of FIG. 9B(d), (e) and (f) T4 ₂ ). At this time, the shunt regulator X operates in the regulated state, so that the gold-oxygen half-field effect transistor M operates correspondingly in the regulated state, and the current through the LED sub-array is stably maintained. .

After the input voltage vi half cycle, the input voltage vi begins to drop to And However, while still overcoming the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), the shunt regulator Xe is turned off, the gold-oxygen half-field effect transistor Me Turn on. Moreover, the shunt regulator Xj is turned on, and the gate potential of the gold-oxygen half-field effect transistor Mj is pulled off and turned off. At this time, the resistor Rx is connected in parallel with Re1 (the resistance is Rx∥ Re1), and the current through the LED sub-array is increased from I4 ^L to (corresponding to time t5 _{1 of} part (d), (e) and (f) of Fig. 9B.

When the input voltage vi continues to drop to And However, when the forward voltage drop of all LED sub-arrays is overcome (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), the shunt regulators Xe and Xj are both turned off, and the gold-oxygen half-field effect The transistors Me and Mj are both turned on, and the resistors Rx, Re1 and Rj1 are connected in parallel (wherein the resistance value of Rx ∥ Re1 ∥ Rj1 < the resistance value of Rx ∥ Re1 < Rx) has a lower equivalent resistance, so that The current of the LED sub-array rises from I4 ^M to I4 ^H (time t5 ₂ ), and the current through the LED sub-array is stabilized at I4 ^H until the input voltage vi continues to fall without overcoming the forward voltage drop of all LED sub-arrays (vi< V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), the current through the LED sub-array drops from I4 ^H to I3 (time t5).

Please refer to FIG. 8E, which illustrates an embodiment of a line voltage regulation rate reducer 140a in accordance with another embodiment of the present invention. The current regulator 120 of FIG. 8E is the same as or similar to the embodiment of the line voltage regulation rate reducer 140a, and the main difference is that the current regulator 120 and the line voltage adjustment rate tightener 140a of FIG. 8E are disposed on The current sense resistor 160 is between the cathode terminal of the LED array.

FIG. 8E of the embodiments, it is assumed to ignore a sinusoidal voltage compensator (R1 and R2) and across the current detecting resistor 160 of the voltage across the ₁₆₀ V, the resistance of the resistor Re3 and Re4 (detection voltage dividing resistors) the mainly detection node When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), during this period, the bypass switches S1, S2 and S3 All are conductive. The voltage divided by the node of the resistor Re3 and the resistor Re4 is the input voltage vi minus the forward voltage drop V _G of all the LED sub-arrays, and then the voltage is divided by the resistor Re3 and the resistor Re4 (ie, This feature is similar to that of FIG. 8A, and indicates that the line voltage adjustment rate tightener 140a of FIG. 8E detects the input voltage vi in a similar manner to the detection mode of FIG. 8A, and the control manner thereof will not be described again. In other words, regardless of whether the current regulator 120 and the line voltage regulation rate reducer 140a are disposed on the input side vi side or the low side, the effect of the operation is not affected.

Referring to the embodiment of FIG. 8F, the line voltage regulation rate reducer 146a may include a shunt resistor Ra5, a voltage detecting voltage dividing resistor (resistor Re3 and resistor Re4), a control circuit 142, and a MOS field effect transistor M5. Ignore assumed sinusoidal voltage compensator (R1 and R2) and across the current detecting resistor 160 across the voltage V _160, the resistance of the resistor Re3 and Re4 (detection voltage dividing resistors) coupled to the nodes simultaneously via the input 100 of the rectifier and voltage vi The input end of the control circuit 142 is configured to detect the input voltage vi and supply the divided voltage of the input voltage vi to the control circuit 142. The current regulator 120 is disposed between the current detecting resistor 160 and the cathode end of the LED array, and the source of the metal oxide half field effect transistor M in the current regulator 120 is coupled to the gold oxide half field effect transistor M5 through the resistor Re5. The gate of the MOSFET and the gate of the MOS transistor M5 is coupled to the output of the control circuit 142.

In this embodiment, when the input voltage vi has not overcome the forward voltage drop of all LED sub-arrays (vi < V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ) and is at a relatively low voltage, control The circuit 142 detects that the input voltage vi is divided by the node of the resistor Re3 and the resistor Re4, so that the gold-oxygen half-field effect transistor M5 is constantly turned on. At this time, the parallel regulator X detects the resistance of the resistor Rx∥Re5 and then switches to the conduction. Between the cut-off and the cut-off, the gold-oxide half-effect transistor M is switched to be turned off and on to enter the regulated state, and the current passing through the LED sub-array is controlled by the resistance (Rx ∥ Re5) of the resistor Rx in parallel with Re5.

When the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ) and is at a relatively high voltage, the gold-oxygen half-field effect at this time The crystal M5 is similar to a variable resistor. The control circuit 142 detects that the input voltage vi is divided by the node of the resistor Re3 and the resistor Re4, so that the channel of the metal oxide half field effect transistor M5 is turned off by conduction. That is, the channel resistance of the MOS field-effect transistor M5 gradually becomes larger, and the change in the resistance value changes continuously and smoothly. At this time, the current regulator 120 regulates the current through the LED sub-array, and the current is controlled by the resistance of the resistor Rx and the resistor Re5 and the resistance of the MOS field M5 ( R _{M 5} ) and the parallel resistance. The resistance value is Rx∥(Re5+ R _{M 5} ), and the resistance value R _{M 5 of the} gold-oxygen half-field effect transistor M5 is changed by the change of the input voltage vi. In other words, when the input voltage vi overcomes the forward voltage drop of all LED sub-arrays (in the relatively high voltage region), the current through the LED sub-array is regulated by the equivalent resistance value Rx∥(Re5+ R _{M 5} ), etc. The range of the effect resistance value is Rx ∥ Re5 < Rx ∥ (Re5 + R _{M 5} ) < Rx. When the input voltage vi is raised by (vi < V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ) ( (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _{When G} ), the channel resistance value R _{M 5 of the} gold-oxygen half-field effect transistor M5 is the smallest (close to 0). At this time, it has the smallest equivalent resistance value Rx∥(Re5+ R _{M 5} ), which is only slightly larger than Rx∥Re5. As the input voltage vi continues to rise, the channel of the gold-oxygen half-field effect transistor M5 is turned off by conduction, and the channel resistance R _{M 5} is also gradually increased, so that the equivalent resistance value Rx ∥ (Re5+ R _{M 5} ) also becomes larger. The current through the LED sub-array will gradually decrease. When the input voltage vi continues to rise until the channel of the gold-oxygen half-effect transistor M5 is completely turned off ( R _{M 5 is} close to ∞) and the circuit is broken, the equivalent resistance value is Rx, so that the current passing through the LED sub-array is controlled by the resistance of the resistor Rx. .

Referring next to FIG. 8G, the current regulator 120 is coupled to the line voltage regulation rate reducer 148a. The line voltage regulation rate tightener 148a is coupled to the resistor Rx of the current regulator 120 through the resistor Re1 and the resistor Rk1. The line voltage adjustment rate tightener 148a further includes a metal oxide half field effect transistor Me and Mk, a resistor Re2, a resistor Re3, and a resistor. Re4, resistor Rk2, resistor Rk3 and resistor Rk4, shunt regulators Xe and Xk, Zener diodes Ze and Zk. In this embodiment, it is assumed negligible cross voltage V sinusoidal voltage compensator ₁₆₀ (R1 and R2), and both ends of the current detection resistor 160, when the input voltage vi overcome all the sub-arrays LED forward voltage drop (vi> V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ) and but When Vth _Xe is the threshold voltage of the shunt regulator Xe, Vth _Xk is the threshold voltage of the shunt regulator Xk, Vth _Xe is the same or similar to Vth _Xk , and ), the shunt regulators Xe and Xk are both turned off, and the gold-oxygen half-field effect transistors Me and Mk are both turned on, so that both Re1 and Rk1 are bypassed, so that the current regulator 120 is controlled by the minimum equivalent resistance Rx, and provides maximum The equivalent current I4 ^H .

When the input voltage vi rises to overcome the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), and but When the shunt regulator Xe is turned on but the shunt regulator Xk is turned off, the gold-oxygen half field effect transistor Me is turned off but the gold-oxygen half field effect transistor Mk is turned on, so that Rk1 is bypassed, and the equivalent resistance is the resistance Rx series resistance Re1 (resistance Rx +Re1), providing the corresponding equivalent current I4 ^M (current I4 ^M <I4 ^H ).

When the input voltage vi continues to rise to overcome the forward voltage drop of all LED sub-arrays (vi > V _{G 1} + V _{G 2} + V _{G 3} + V _{G 4} = V _G ), And When the parallel regulators Xe and Xk are both turned on, the metal oxide half field effect transistors Me and Mk are cut off, so that the equivalent resistance is the resistance Rx series resistance Re1 and then the series Rk1 (resistance Rx+Re1+Rk1), corresponding to the equivalent current Is I4 ^L (current I4 ^L <I4 ^M <I4 ^H ).

During the second half of the input voltage vi, the input voltage vi begins to decrease, so that the parallel regulators Xk and Xe are successively turned off by the original conduction state, and the equivalent resistance is reduced from the resistance value (Rx+Re1+Rk1) to the resistance value. (Rx+Re1), which will be as low as the resistance value (Rx), so that the corresponding equivalent current rises from I4 ^L to I4 ^M and then rises to I4 ^H .

Please refer to FIGS. 8D-8G and FIG. 9B at the same time. In the embodiment, after the current voltage adjustment ratios 140a, 140a and 145a, 146a or 148a are set by the current I0~I3 of the LED sub-array ((d) of FIG. 9B, (e) and (f) part of the waveform) and the line voltage adjustment rate tighteners 140a, 140a and 145a, 146a or 148a before setting (waveforms of parts (a), (b) and (c) of Fig. 9B) Substantially the same, indicating that the line voltage regulation rate reducers 140a, 140a and 145a, 146a or 148a are arranged to change the input voltage to overcome the forward voltage drop of all LED sub-arrays, dividing the current I4 through the LED sub-array into I4. ^H , I4 ^M and I4 ^L , and I4=I4 ^H >I4 ^M >I4 ^L >I3>I2>I1. The higher the effective value of the input voltage vi, the larger the slope of the rising edge and the falling edge of the waveform of the input voltage vi, indicating the time t4 to t4 ₁ of the current I4 ^H passing through the LED sub-array and The shorter the interval between t5 ₂ and t5, the longer the interval between the times t4 ₁ to t4 ₂ and t5 ₁ to t5 ₂ and/or t4 ₂ to t5 ₁ of the current I4 ^M and/or I4 ^L passing through the LED sub-array. Therefore, the integrated area of the current I _LED and the time passing through the LED sub-array can be adjusted to stabilize the average current without being affected by the effective value of the input voltage vi. In an embodiment, the number of line voltage regulation rate reducers may be n steps such that current I4 through the LED sub-array is divided into n+1 steps.

10A and 10B are schematic circuit diagrams showing different embodiments of an electronic control unit of the LED light engine of FIG. 1A. Referring first to FIG. 10A, the electronic control device of the LED light engine includes a plurality of scintillation suppression capacitors Cg1, Cg2, Cg3, and Cg4, and a plurality of diodes Dg1, Dg2, Dg3, and Dg4, and respective scintillation suppression capacitors Cg1 and Cg2. Cg3 and Cg4 are respectively connected in parallel to the corresponding external LED sub-arrays G1, G2, G3 and G4, and the cathodes of the respective diodes Dg1, Dg2, Dg3 and Dg4 are coupled to the corresponding external LED sub-arrays G1, G2, G3 and G4 The anode. In an embodiment, the embodiment of the flicker suppression capacitor can be implemented by an M×N matrix composed of non-electrolytic capacitors. For example, non-electrolytic capacitors such as ceramic capacitors, tantalum capacitors, and solid-state capacitors can be used to establish non-electrolytic capacitors of M columns. To establish a voltage rating and establish a current rating through a column of non-electrolytic capacitors, thus avoiding the use of short-lived electrolytic capacitors. Of course, electrolytic capacitors can also be used as the scintillation suppression capacitors Cg1, Cg2, Cg3, and Cg4, regardless of the length of use.

Hereinafter, the manner in which the blink suppression capacitors Cg1, Cg2, Cg3, and Cg4 are turned on and off in the zero initial state (ie, full discharge) during the first period of the input voltage will be described.

In the first half of the cycle, when the channels of the bypass switches S15, S25 and S35 are established and are turned into a series of bypass switch columns, the diodes Dg1 to Dg4 are biased, and the input voltage vi is transmitted through the diodes Dg1 to Dg4. The flicker suppression capacitors Cg1 to Cg4 are respectively charged. At this stage, the flicker suppression capacitors Cg1 to Cg4 are charged in series. When the input voltage vi until the last LED overcome the G4 sub-array along a forward voltage drop (V _G4), Cg4 flicker suppression capacitor charging voltage V _G4 green sustain voltage V _G4. At this time, the input voltage vi continues to pass through the diodes Dg1 to Dg3 to charge the flicker suppression capacitors Cg1 to Cg3, and the input current illuminates G4 and passes through the current detecting resistor 160.

When the input voltage vi rises to overcome the forward voltage drop (V _G3 + V _G4 ) of the inverse two-stage LED sub-arrays G3 and G4, and the forward voltage drop (V _G3 + V _G ) between the LED sub-arrays G3 and G4 When there is a forward voltage drop (V _G2 + V _G3 + V _G4 ) between the LED sub-arrays G2, G3 and G4, the bypass switch S35 is turned off, the bypass switch S25 is turned into an adjusted state, and the input current is passed through the bypass switch S15. After S25, the LED sub-arrays G3 and G4 are turned on and turned on. At this time, the flicker suppression capacitor Cg3 is charged to the voltage V _{G3 and} then maintained at the voltage V _G3 . At this time, the input voltage vi continues to charge the flicker suppression capacitors Cg1 and Cg2 through the diodes Dg1 and Dg2.

When the input voltage vi rises to overcome the forward voltage drop of the LED sub-arrays G2, G3, and G4 (V _G2 + V _G3 + V _G4 ), and the forward voltage drop between the LED sub-arrays G2, G3, and G4 (V _{G2 )} +V _G3 +V _G4 ) and the forward voltage drop (V _G1 +V _G2 +V _G3 +V _G4 ) between the first to fourth LED sub-arrays G1, G2, G3 and G4, the bypass switch S25 and S35 is cut off, the bypass switch S15 is turned into an adjusted state, and the input current is passed through the bypass switch S15 to the LED sub-arrays G2, G3 to the LED sub-array G4 to illuminate the LED sub-arrays G2, G3, and G4, and the flicker suppression capacitor Cg2 is charged to the voltage. V _{G2 is} maintained at voltage V _G2 . At this time, the input voltage vi continues to charge the flicker suppression capacitor Cg1 through the diode Dg1.

Until the input voltage vi rises to overcome the forward voltage drop (V _G1 +V _G2 +V _G3 +V _G4 ) of all the LED sub-arrays G1, G2, G3 and G4, the flicker suppression capacitor Cg1 is maintained after being charged to the voltage V _G1 . At voltage V _G1 . At this time, since the bipolar junction transistors B1, B2, and B3 are all in the on state, the bypass switches S15, S25, and S35 are all turned off, and the input current is passed through the LED sub-arrays G1, G2, and G3 to the LED sub-array G4 to The first to fourth stage LED sub-arrays G1, G2, G3, and G4 are lit and passed through the current detecting resistor 160. Current regulator 120 maintains the current through LED sub-arrays G1, G2, G3 through G4 at I4.

In the second half of the cycle, the input voltage vi begins to drop to overcome the forward voltage drop (V _G2 + V _G3 + V _G4 ) of the third-order LED sub-arrays G2, G3, and G4, and is interposed between the LED sub-arrays G2, G3 and Forward voltage drop of G4 (V _G2 +V _G3 +V _G4 ) and forward voltage drop of first to fourth LED sub-arrays G1, G2, G3 and G4 (V _G1 +V _G2 +V _G3 +V _G4 ) Between the diodes Dg1 is reverse biased, and the flicker suppression capacitor Cg1 is discharged to illuminate the LED sub-array G1. At this time, the dual-carrier junction transistors B2 and B3 are all in the on state, the bypass switches S25 and S35 are both turned off, the bypass switch S15 is turned into the regulation state, and the input current is turned on by the bypass switch S15 to turn the third-order LED Sub-arrays G2, G3, and G4 pass through current sense resistor 160 to maintain the current through LED sub-arrays G2, G3, and G4 at I3.

As the input voltage vi continues to drop to overcome the forward voltage drop (V _G3 + V _G4 ) of the countdown secondary LED sub-arrays G3 and G4, and the forward voltage drop between the reciprocal secondary LED sub-arrays G3 and G4 ( between V _G3 + V _G4) and the sub-array LED G2, G3 and G4 of three reciprocal cis forward voltage drop _{(V G2 + V G3 + V} G4), diodes Dg1 and Dg2 reverse bias. The flicker suppression capacitors Cg1 and Cg2 are respectively discharged to illuminate the LED sub-arrays G1 and G2. At this time, the voltage across the current detecting resistor 160 is insufficient to turn on the bipolar junction transistor B1, and the bypass switch S15 is turned into an on state. At the same time, the bipolar contact transistor B2 detects the voltage across the voltage detecting resistor 160 through the anti-clamping resistor Rx2, and pulls down the voltage between the gate and the source of the bypass switch S25 to turn off the bypass switch S25, and flows through the current. The current of the detecting resistor 160 drops, the bipolar junction transistor B2 is turned off, the bypass switch S25 is turned on again and enters the regulation state, the bipolar junction transistor B3 is in the on state, the bypass switch S35 is turned off, and the input current I2 is turned off. The LED sub-arrays G3 and G4 are lit by the bypass switches S15 and S25, and passed through the current detecting resistor 160.

Vi with the input voltage continues to drop to overcome the last stage G4 of the LED arrays to the sub-cis voltage drop (V _G4), and G4 between the sub-arrays of LED forward voltage drop (V _G4) and the last two sub-array LED G3 and G4 During the forward voltage drop (V _G3 + V _G4 ), the diodes Dg1, Dg2, and Dg3 are reversely biased, and the flicker suppression capacitors Cg1, Cg2, and Cg3 are respectively discharged to illuminate the LED sub-arrays G1, G2, and G3. At this time, the voltage across the current detecting resistor 160 is insufficient to turn on the bipolar junction transistors B1 and B2, and the bypass switches S15 and S25 are respectively turned into an on state. The bipolar junction transistor B3 detects the voltage across the current detecting resistor 160 through the anti-clamping resistor Rx3, and then quickly switches between the on state and the off state, so that the bypass switch S35 enters the regulation state correspondingly, and the input current I1 passes through The LED sub-array G4 is lit and passed through the current detecting resistor 160.

After the first cycle of the input voltage, the initial states of the flicker suppression capacitors Cg1, Cg2, Cg3, and Cg4 are established and reach a steady state (charge completion). The following describes the manner in which the LED sub-array is turned on and off during steady state. . In the first half of a cycle, when the input voltage vi is smaller than the forward voltage drop (V _G4 ) of the last LED sub-array G4, the diodes Dg1, Dg2, Dg3, and Dg4 are reverse biased, and the flicker suppression capacitors Cg1, Cg2, Cg3, and Cg4 Discharge to illuminate the LED sub-arrays G1, G2, G3, and G4, respectively, to avoid dead time.

When the input voltage vi rises to overcome a last sub-LED arrays along the G1 to the voltage drop (V _G4), and the last one is interposed along G4 sub-array of LED forward voltage drop (V _G4) and the last two sub-LED arrays and G3 Between the forward voltage drop of G4 (V _G3 + V _G4 ), the diodes Dg1, Dg2, and Dg3 are reversely biased, and the flicker suppression capacitors Cg1, Cg2, and Cg3 are discharged to illuminate the LED sub-arrays G1, G2, and G3, respectively. The diode Dg4 is biased, the input current illuminates the last stage LED sub-array G4, and the flicker suppression capacitor Cg4 is recharged to the voltage V _G4 and passed through the current sense resistor 160. The double carrier junction transistor B3 detects the voltage across the current detecting resistor 160 through the anti-clamping resistor Rx3 and switches between the conduction and the off, so that the bypass switch S35 is quickly switched between the off and the conduction to enter the regulation state. The current through LED sub-array G4 is maintained at I1.

When the input voltage vi rises to overcome the forward voltage drop (V _G3 + V _G4 ) of the reciprocal secondary LED sub-arrays G3 and G4, and the forward voltage drop between the reciprocal secondary LED sub-arrays G3 and G4 (V) _{When G3} +V _G4 ) is between the forward voltage drop (V _G2 +V _G3 +V _G4 ) of the third-order LED sub-array G2, G3 and G4, the diodes Dg1 and Dg2 are reverse biased, and the flicker suppression capacitor Cg1 And Cg2 discharge to illuminate the LED sub-arrays G1 and G2, respectively. At the same time, the diode Dg3 is biased, the input current is passed through the bypass switches S15 and S25 to the LED sub-array G3 to the LED sub-array G4 to illuminate the LED sub-arrays G3 and G4, and the flicker suppression capacitors Cg3 and Cg4 are respectively recharged to Voltages V _G3 and V _G4 . At this time, the input current passes through the current detecting resistor 160, and the bipolar contact transistor B2 detects the voltage across the current detecting resistor 160 through the anti-clamping resistor Rx2, and then quickly switches between the conducting and the off, so that the bypass switch S25 Corresponding to switching between off and on, enters the regulated state to maintain the current through LED sub-arrays G3 and G4 at I2. The double carrier junction transistor B3 detects the constant conduction of the voltage across the current detecting resistor 160 through the anti-clamping resistor Rx3, so that the bypass switch S35 is always turned off.

When the input voltage vi rises to overcome the forward voltage drop of the third-order LED sub-arrays G2, G3, and G4 (V _G2 +V _G3 +V _G4 ), and is in the third-order LED sub-arrays G2, G3, and G4 The forward voltage drop (V _G2 +V _G3 +V _G4 ) and the forward voltage drop of the reciprocal four-level LED sub-arrays G1, G2, G3, and G4 (V _G1 +V _G2 +V _G3 +V _G4 ) When the diode Dg1 is reverse biased, the flicker suppression capacitor Cg1 is discharged to illuminate the LED sub-array G1. At the same time, the diode Dg2 is biased, the input current passes through the bypass switch S15 to the LED sub-arrays G2, G3 to the LED sub-array G4, and the flicker suppression capacitors Cg2, Cg3 and Cg4 are recharged to the voltages V _G2 , V _G3 and V _G4 . The input current illuminates the LED sub-arrays G2, G3, and G4 and passes through the current sense resistor 160. The bipolar junction transistor B1 detects the voltage across the current detecting resistor 160 through the anti-clamping resistor Rx1 and then switches between the on and the off, and the bypass switch S15 switches between the off and the on and enters the regulated state. The current through the LED sub-arrays G2, G3, and G4 is maintained at I3. At this time, the bipolar-substrate transistors B2 and B3 respectively detect the cross-voltage of the current detecting resistor 160 through the anti-clamping resistors Rx2 and Rx3, and then make the bypass switches S25 and S35 constantly cut off.

When the input voltage vi rises to overcome the forward voltage drop (V _G1 +V _G2 +V _G3 +V _G4 ) of all the LED sub-arrays G1, G2, G3 and G4, the diode Dg1 is biased, and the input current is passed through the LED. Sub-arrays G1, G2, and G3 to LED sub-array G4 to illuminate all of the LED sub-arrays and pass current sense resistor 160. The input voltage vi recharges the flicker suppression capacitor Cg1 to the voltage V _G1 . At this time, the dual-carrier junction transistors B1, B2, and B3 respectively pass the anti-clamping resistors Rx1, Rx2, and Rx3 to detect the constant conduction of the current detecting resistor 160, and the bypass switches S15, S25, and S35 are always cut off. The current regulated by the current regulator 120 through the LED sub-arrays G1, G2, G3, and G4 is maintained at I4.

After the input voltage vi begins to decrease in the second half of the cycle, the manner in which the LED sub-array is turned on and off is similar to the manner in which the LED sub-array is turned on and off in the initial state described above, and thus will not be described again.

Referring to FIG. 10B, the electronic control device of the LED light engine includes a plurality of scintillation suppression capacitors Cg1', Cg2', Cg3', and Cg4', and a plurality of diodes Dg1, Dg2, Dg3, and Dg4, and each of the flicker suppression capacitors. Cg1', Cg2', Cg3' and Cg4' are respectively connected in parallel to a plurality of external LED sub-arrays G1, G2, G3 and G4 in series; a plurality of external LED sub-arrays G2, G3 and G4 are connected in series; The external LED sub-arrays G3 and G4; and a corresponding one of the external LED sub-arrays G4, and the cathodes of the respective diodes Dg1, Dg2, Dg3 and Dg4 are coupled to the corresponding external LED sub-arrays G1, G2, G3 and G4 anode. The implementation of the flicker suppression capacitor can be implemented by an M×N matrix composed of an electrolytic capacitor or a non-electrolytic capacitor. The type of the non-electrolytic capacitor has been described above, and will not be described again.

Hereinafter, the manner in which the blink suppression capacitors Cg1', Cg2', Cg3', and Cg4' are turned on and off in the zero initial state (i.e., full discharge) during the first period of the input voltage will be described.

In the first half of a cycle, when the channels of the bypass switches S15, S25, and S35 are established and both are turned on to form a series of bypass switch columns, the input voltage vi passes through the diodes Dg1 to Dg4 to respectively respectively blink the suppression capacitor Cg1'~ Cg4 'mechanism of charging is similar to 10A, the difference being that the flicker suppression capacitor Cg4' charged to a voltage V _G4 is maintained at a voltage V _G4, flicker suppression capacitor Cg3 'charged to the voltage V _G3 + after V _G4 is maintained at a voltage V _G3 +V _G4 , flicker suppression capacitor Cg2' is charged to voltage V _G2 +V _G3 +V _G4 and is maintained at voltage V _G2 +V _G3 +V _G4 , and the flicker suppression capacitor Cg1' is charged to voltage V _G1 +V _G2 +V _G3 + After V _{G4 is} maintained at voltage V _G1 +V _G2 +V _G3 +V _G4 .

In the second half of the cycle, the input voltage vi begins to drop to overcome the forward voltage drop (V _G2 + V _G3 + V _G4 ) of the third-order LED sub-arrays G2, G3, and G4, and is interposed between the LED sub-arrays G2, G3 and Forward voltage drop of G4 (V _G2 +V _G3 +V _G4 ) and forward voltage drop of first to fourth LED sub-arrays G1, G2, G3 and G4 (V _G1 +V _G2 +V _G3 +V _G4 ) Between the diodes Dg1 is reverse biased, and the flicker suppression capacitor Cg1' is discharged to supply the discharge current I4' to the LED sub-arrays G1 to G4. At this time, the bypass switch S15 is turned from the off state to the regulated state, the bypass switches S25 and S35 are maintained in the off state, and the input current is turned on by the bypass switch S15 to turn on the third-order LED sub-arrays G2, G3, and G4, and the current is passed. Resistor 160 is sensed to provide current I3 to LED sub-arrays G2, G3, and G4. That is, the current through the LED sub-array G1 at this stage is I4', and the current I4'+I3 through the LED sub-arrays G2, G3, and G4.

As the input voltage vi continues to drop to overcome the forward voltage drop (V _G3 + V _G4 ) of the countdown secondary LED sub-arrays G3 and G4, and the forward voltage drop between the reciprocal secondary LED sub-arrays G3 and G4 ( between V _G3 + V _G4) and the sub-array LED G2, G3 and G4 of three reciprocal cis forward voltage drop _{(V G2 + V G3 + V} G4), diodes Dg1 and Dg2 reverse bias. The flicker suppression capacitor Cg1' is discharged to provide the LED sub-arrays G1~G4 discharge current I4', and the flicker suppression capacitor Cg2' is discharged to provide the LED sub-arrays G2~G4 discharge current I3'. At this time, the bypass switch S15 is turned to the on state, the bypass switch S25 enters the regulation state, the bypass switch S35 is turned off, and the input current supplies the current I2 to the LED sub-arrays G3 and G4 and the current detecting resistor 160 via the bypass switches S15 and S25. . At this stage, the current through the LED sub-array G1 is I4', the current through the LED sub-array G2 is I4'+I3', and the current through the LED sub-arrays G3 and G4 is I4'+I3'+I2.

Vi with the input voltage continues to drop to overcome the last stage G4 of the LED arrays to the sub-cis voltage drop (V _G4), and G4 between the sub-arrays of LED forward voltage drop (V _G4) and the last two sub-array LED G3 and G4 During the forward voltage drop (V _G3 +V _G4 ), the diodes Dg1, Dg2 and Dg3 are reverse biased, and the flicker suppression capacitors Cg1', Cg2' and Cg3' are respectively discharged to illuminate the LED sub-arrays G1, G2 and G3. . Specifically, the flicker suppression capacitor Cg1' is discharged to provide the LED sub-arrays G1 to G4 discharge current I4', and the flicker suppression capacitor Cg2' is discharged to provide the LED sub-arrays G2 to G4 discharge current I3'. The flicker suppression capacitor Cg3' is discharged to provide the LED sub-array G3~G4 discharge current I2'. At this time, the bypass switches S15 and S25 are respectively turned into an on state, the bypass switch S35 correspondingly enters an adjustment state, and the input current passes through the bypass switches S15 to S35 and provides an input current I1 to illuminate the LED sub-array G4. At this stage, the current through the LED sub-array G1 is I4', the current through the LED sub-array G2 is I4'+I3', the current through the LED sub-array G3 is I4'+I3'+I2', and through the LED sub-array The current of G4 is I4'+I3'+I2'+I1.

After the first cycle of the input voltage, the initial states of the flicker suppression capacitors Cg1', Cg2', Cg3', and Cg4' are established and reach steady state (charge completion). The following illustrates the illumination of the LED sub-array during steady state. With the way to extinguish. In the first half of a cycle, when the input voltage vi is smaller than the forward voltage drop (V _G4 ) of the last LED sub-array G4, the diodes Dg1, Dg2, Dg3, and Dg4 are reverse biased, and the flicker suppression capacitors Cg1', Cg2', and Cg3 'And Cg4' are discharged separately to illuminate the LED sub-arrays G1~G4, G2~G4, G3~G4 and G4 to avoid dead time.

When the input voltage vi rises to overcome a last sub-LED arrays along the G1 to the voltage drop (V _G4), and the last one is interposed along G4 sub-array of LED forward voltage drop (V _G4) and the last two sub-LED arrays and G3 Between the forward voltage drop of G4 (V _G3 +V _G4 ), the diodes Dg1, Dg2 and Dg3 are reversed, and the flicker suppression capacitors Cg1', Cg2' and Cg3' are respectively discharged, respectively providing current I4' and current I3'. And the current I2' to illuminate the LED sub-arrays G1~G4, G2~G4, and G3~G4. At this time, the diode Dg4 is biased, the input current illuminates the last-stage LED sub-array G4, and the flicker suppression capacitor Cg4' is recharged to the voltage V _G4 . And, the bypass switch S35 enters an adjustment state to provide a current I1 to the LED sub-array G4.

When the input voltage vi rises to overcome the forward voltage drop (V _G3 + V _G4 ) of the reciprocal secondary LED sub-arrays G3 and G4, and the forward voltage drop between the reciprocal secondary LED sub-arrays G3 and G4 (V) _{When G3} +V _G4 ) is between the forward voltage drop (V _G2 +V _G3 +V _G4 ) of the third-order LED sub-array G2, G3 and G4, the diodes Dg1 and Dg2 are reverse biased, and the flicker suppression capacitor Cg1 'And Cg2' discharges to illuminate the LED sub-arrays G1~G4 and G2~G4 with current I4' and current I3', respectively. The diode Dg3 is biased, and the input current is passed through the bypass switches S15 and S25 to the LED sub-arrays G3 and G4 to illuminate the LED sub-arrays G3 and G4, and recharge the flicker suppression capacitors Cg3' and Cg4' to the voltage V _{G3, respectively.} And V _G4 . At this time, the bypass switch S35 is always turned off, the bypass switch S25 enters the regulation state, and the current I2 is supplied through the LED sub-arrays G3 and G4.

When the input voltage vi rises to overcome the forward voltage drop of the third-order LED sub-arrays G2, G3, and G4 (V _G2 + V _G3 + V _G4 ), and is in the third-order LED sub-arrays G2, G3, and G4 The forward voltage drop (V _G2 +V _G3 +V _G4 ) and the forward voltage drop of the reciprocal four-level LED sub-arrays G1, G2, G3, and G4 (V _G1 +V _G2 +V _G3 +V _G4 ) When the diode Dg1 is reverse biased, the flicker suppression capacitor Cg1' discharges to provide the current I4' to illuminate the LED sub-arrays G1 to G4. At the same time, the diode Dg2 is biased, and the input current is passed through the bypass switch S15 to the LED sub-arrays G2, G3 and G4, and the main voltages V _G2 and V _{G3 are} recharged to the flicker suppression capacitors Cg2', Cg3' and Cg4'. V _G4 . The bypass switch S15 enters an adjusted state to provide current I3 to the LED sub-arrays G2, G3, and G4. At this time, the bypass switches S25 and S35 are always turned off.

When the input voltage vi rises to overcome the forward voltage drop (V _G1 +V _G2 +V _G3 +V _G4 ) of all the LED sub-arrays G1, G2, G3 and G4, the diode Dg1 is biased, and the input current is passed through the LED. Sub-arrays G1, G2, G3, and G4 illuminate all of the LED sub-arrays and pass current sense resistor 160. The input voltage vi recharges the flicker suppression capacitor Cg1' to the voltage V _G1 . At this time, the bypass switches S15, S25, and S35 are constantly turned off, and are regulated by the current regulator 120 to supply the current I4 through the LED sub-arrays G1, G2, G3, and G4.

After the input voltage vi begins to decrease in the second half of the cycle, the manner in which the LED sub-array is turned on and off is similar to the manner in which the LED sub-array is turned on and off in the initial state described above, and thus will not be described again. In an embodiment, the flicker suppression capacitor can also effectively improve the flicker percentage flicker and flicker index while maintaining high power factor and low harmonic distortion.

FIG. 10C is a diagram showing the comparison of the input voltage, the input current, and the current through the LED sub-array with respect to the time axis before and after the flicker suppression capacitor and the diode are set, in which the electronic control device of the LED light engine of FIG. 10A is compared. (a) and (b) of FIG. 10C respectively show a waveform comparison diagram of the input voltage Vin and the input current Iin with respect to time t before and after the setting of the scintillation suppression capacitor and the diode of FIG. 10A, and FIG. 10C(c) And (d) respectively show the waveform comparison of the input voltage Vin and the current I _LED passing through the LED sub-array with respect to time t before and after the flicker suppression capacitor and the diode arrangement as shown in FIG. 10A, and FIG. 10C(e) And (f) are respectively a waveform comparison diagram of the light output intensity (Light Intensity) with respect to time t before and after the setting of the scintillation suppression capacitor and the diode in FIG. 10A. According to the characteristics of the LED light source, the current I _LED through the LED sub-array has a linear relationship with the light output intensity, so the waveforms of (e) and (f) of FIG. 10C and the waveforms of (c) and (d) of FIG. 10C, respectively. Similar. In addition, the electronic control device of the LED light engine of FIG. 10B functions similarly to the electronic control device of the LED light engine of FIG. 10A, with the difference being the cut-off potential of each of the flicker suppression capacitors and the number of LED sub-arrays supplied during discharge. Therefore, the electronic control device of the LED light engine of FIG. 10B is similar to the waveform comparison diagram of the input voltage, the input current, and the current through the LED sub-array with respect to the time axis before and after the flicker suppression capacitor and the diode are disposed, and is similar to FIG. 10A. This is not to be repeated.

Referring to FIGS. 10A, 10B and 10C (a) and (b), the waveform of the input current Iin is hardly changed before and after the flicker suppression capacitor and the diode are set, indicating the flicker suppression capacitor and the diode setting. After that, the power factor is similar to the harmonic distortion before the flicker suppression capacitor and the diode are set. In other words, the power factor is reduced or the harmonic distortion is not increased because the flicker suppression capacitor and the diode are set. After the flicker suppression capacitor of FIG. 10A or 10B is set, since the respective flicker suppression capacitors are only charged to the total forward voltage drop of one or more LED sub-arrays corresponding thereto, the setting of the flicker suppression capacitor does not affect. Rectified sinusoidal input voltage and total LED The comparison of the forward voltage drop of the array does not of course affect the operating state of the bypass switch, thus maintaining a high power factor and low total harmonic distortion.

Referring to FIGS. 10A, 10B and 10C (c), (d), the waveform of the current I _LED passing through the LED sub-array is significantly changed before and after the flicker suppression capacitor and the diode are disposed. Please refer to part (c) of FIG. 10C first. Before the flicker suppression capacitor and the diode are set, the current I _LED passing through the LED sub-array is similar to the target type, and the input voltage Vin of the waveform is lower. The voltage Vin has not been able to overcome the forward voltage drop of the LED sub-array G4, and no current flows through the LED sub-array G4, defining a dead time t1 during this period.

Referring to part (d) of FIG. 10C, after the flicker suppression capacitor and the diode are set, the current I _LED passing through the LED sub-array G4 is similar to a ripple superimposed on a DC current. . It is worth noting that the input voltage Vin cannot overcome the forward voltage drop of the LED sub-array G4 in the lower part of the input voltage Vin of the waveform, but the flicker suppression capacitor (shown in FIG. 10A) can provide current to the point. Bright LED sub-array G4. Therefore, in part (d) of FIG. 10C, the input voltage Vin is smaller than the interval of the forward voltage drop (V _G1 ) of the LED sub-array G4, corresponding to the time on the current I _LED waveform diagram of the LED sub-array G4. Within t1', the current I _LED through LED sub-array G1 is still greater than zero (current is provided by the flicker suppression capacitor). In other words, the flicker suppression capacitor and the setting of the diode can avoid the occurrence of dead time t1.

Please refer to part (e) of Fig. 10C, which shows the maximum value Lmax and the minimum value Lmin of the light output L waveform between one period T, and defines the average light output (Average Light Output) Lave. The above area is A, and the area below the defined average light output Lave is B. Percent flicker is commonly used to measure the quality of fluorescent lamps, as defined by the Modified IES Lighting Handbook. The flicker index can be used to measure the quality of the LED. The formula is In general, the value of the scintillation index is preferably less than one thousandth (12%) of the LED current waveform frequency (for example, 120 Hz).

Please refer to part (f) of FIG. 10C, where the maximum value Lmax' and the minimum value Lmin' of the light output L' waveform are indicated, and the area above the average light output Lave' is defined as A', and the average light output is defined. 'The area below is B'. By definition, the percentage blinking at this time is , the flicker index is . Comparing the waveforms of parts (e) and (f) of Figure 10C, it is obvious that And . That is to say, after the flicker suppression capacitor and the diode are set, the percentage flicker and the flicker index both decrease significantly.

In summary, in one embodiment, when the input voltage overcomes the sum of the forward voltage drops of the current stage (eg, LED sub-array G3) and the external LED sub-array below the current level, but does not overcome the upper stage (eg, LED) When the sum of the forward voltage drops of the sub-array G2) and the external LED sub-array below the upper stage, the input current illuminates the external LED sub-array of the current level and below, and the flicker suppression capacitors (for example, Cg1 and Cg2) are discharged. The external LED sub-arrays of the upper and upper levels are illuminated (for example, LED sub-arrays G1 and G2). In other words, by setting the flicker suppression capacitor and the diode, it is possible to avoid the dead time caused when the input voltage does not overcome the forward voltage drop of the LED sub-array. Moreover, the percentage flicker and flicker index can be further improved without causing a problem of a decrease in power factor or an increase in harmonic distortion, which can make the illumination quality of the LED array better. The above embodiments in which the scintillation suppression capacitor and the diode are provided can be applied to any embodiment of the present invention.

In summary, the electronic control device of the LED light engine according to the embodiment of the present invention detects the cross-voltage of the current through the LED sub-array through the comparison circuit to adjust the operating state of the corresponding bypass switch. Light-emitting diode light engine electronic control device that illuminates the TED sub-array step by step or stepwise, with simplified circuit, improved power factor and reduced harmonic loss The effect of the truth. An electronic control device for an LED light engine according to an embodiment of the present invention can be connected to an LED array to form a dimmable light-emitting diode lighting device.

The electronic control device of the LED light engine of the present invention can be implemented on an integrated circuit, or can be implemented as a plurality of integrated circuits by a module, and then integrated on a circuit board.

The electronic control device of the LED light engine of the present invention can be integrated with an LED array, wherein the LED array is arranged in parallel with the electronic control device of the LED light engine as an illumination device for the LED sub-array.

The principles, preferred embodiments, and modes of operation of the invention have been described in the foregoing. However, the invention should not be construed as being limited to the specific embodiments discussed. Rather, the above-described embodiments are to be considered as illustrative and not restrictive, and the scope of the invention as defined by the following claims Changes are made to these embodiments.

AC‧‧‧AC voltage source

100‧‧‧Rectifier

120‧‧‧current regulator

150, 152, 154‧‧‧ comparison circuit

M‧‧‧Gold Oxygen Half Field Effect Crystal

X‧‧‧ shunt regulator

Rx1, Rx2, Rx3, Ra, Rx‧‧‧ resistors

R1, R2‧‧‧ sinusoidal voltage compensator

G1, G2, G3, G4‧‧‧ LED sub-arrays

G‧‧‧External LED array

Zd1, Zd2‧‧‧ Zener diode

S1, S2, S3‧‧‧ bypass switch

160‧‧‧current sense resistor

Claims (23)

An electronic control device for an LED light engine, comprising: a rectifier for connecting an external AC voltage source to provide a DC pulse voltage; a bypass switch column coupled to the rectifier and disposed in parallel with an external LED array, the external LED The array includes a plurality of LED sub-arrays connected in series, the bypass switch column includes a plurality of bypass switches connected in series to bypass a corresponding LED sub-array when turned on; a switch control circuit having a current detecting resistor and a plurality of a comparison circuit, the current detecting resistor is coupled between the cathode and the ground of the external LED array, and coupled to the reference ends of the comparison circuits, the comparison circuits respectively have different reference voltages, and the comparison circuits The cross-voltage of the current detecting resistor is compared with each of the reference voltages, and the corresponding bypass switch is turned off or turned on, and the voltage across the current detecting resistor is related to the DC pulse voltage, so that the bypass switch is based on The DC pulse voltage is segmented to illuminate the LED sub-arrays, wherein each of the comparison circuits has a first end, a second end, and the reference end, and the In the comparison circuit, except for the last one comparator circuit, a first terminal coupled to the lower end of the reference circuit comparator comparing circuit superiors. The LED light engine electronic control device of claim 1, wherein the first end of the comparison circuit of the upper stage is coupled to the reference end of the lower level comparison circuit via a Zener diode. The LED light engine electronic control device of claim 1, wherein each of the comparison circuits has a first end, a second end, and the reference end, and the reference terminals of the comparison circuits are coupled to the current The resistance is sensed, and each of the bypass switches is controlled correspondingly to each of the second ends of the comparison circuit. The LED light engine electronic control device of claim 3, wherein the reference terminals of the comparison circuits are connected to the current detecting resistor through an anti-clamping resistor. The LED light engine electronic control device of claim 1, wherein the current detecting resistor comprises a shared current sensing and modulation unit coupled to the external LED array for planning the illuminated external LED sub-array. The current is adjusted to adjust the brightness of the illuminated external LED sub-array, wherein the shared current sensing and modulation unit comprises one of a potentiometer, a voltage controlled resistor or a transistor switch. The LED light engine electronic control device of claim 5, wherein when the shared current sensing and modulation unit comprises the voltage control resistor, the shared current sensing and modulation unit further comprises a pulse width adjustment A variable unit, a low pass filter and a voltage follower. The LED light engine electronic control device according to claim 1, wherein the bypass switch is an N-channel MOSFET or an N-channel junction field effect transistor, and any of the comparison circuits Includes a shunt regulator or a pair of carrier junction transistors. The LED light engine electronic control device of claim 1, further comprising a current regulator coupled to the external LED array for adjusting the input current wave to form a sinusoidal square wave or step A waveform of waves, wherein each of the outer LED sub-arrays is connected to a corresponding bypass switch except for the outer LED sub-array of the last stage, and any one of the bypass switches includes a transistor. The LED light engine electronic control device according to claim 8 , further comprising a line voltage regulation rate compactor coupled to the current regulator, the line voltage adjustment rate compactor comprising a voltage detection parallel regulator or a voltage detecting double carrier junction transistor coupled to the input voltage through a voltage detecting voltage dividing resistor, wherein when the input voltage overcomes all of the external LED subarrays When the voltage drop of the column is reversed, but the reference voltage of the voltage detecting shunt regulator or the voltage detecting bipolar junction transistor has not been overcome, the current through the external LED sub-array is a first current, When the input voltage overcomes the forward voltage drop of all of the external LED sub-arrays and overcomes the reference voltage of the voltage detecting shunt regulator or the voltage detecting bipolar junction transistor, the external LED is illuminated The current of the sub-array is a second current, and the first current is greater than the second current. The LED light engine electronic control device of claim 9, wherein the line voltage adjustment rate tightener is disposed between a cathode of the external LED array and the current detecting resistor, or an anode of the external LED array Between external AC voltage sources. The LED light engine electronic control device of claim 8, further comprising a line voltage regulation rate compactor coupled to the current regulator, the line voltage adjustment rate compactor comprising a voltage detection voltage divider a resistor, a shunt resistor, a transistor, and a control circuit, wherein the shunt resistor is coupled to the current regulator, the transistor is coupled to the shunt resistor, and an input end of the control circuit is coupled to the transistor The output end of the control circuit is coupled to the voltage detecting voltage dividing resistor, and the voltage dividing node of the voltage detecting voltage dividing resistor is coupled to the external AC voltage source. The LED light engine electronic control device according to claim 9, wherein the line voltage adjustment rate compactor further comprises another voltage detecting parallel regulator or another voltage detecting double carrier junction transistor. Through another voltage detecting voltage dividing resistor, coupled to the input voltage, when the input voltage overcomes all of the forward voltage drops of the external LED sub-arrays, but has not overcome the other voltage detecting shunt regulator or the The other voltage detects the reference voltage of the bipolar junction transistor, and does not overcome the reference voltage of the voltage detection shunt regulator or the voltage detection bipolar junction transistor, and the external LED through the illumination The current of the array is the first current, when the input voltage overcomes all of the forward voltage drops of the external LED sub-arrays, and the other voltage is detected to overcome the shunt regulator or the other When detecting the reference voltage of the bipolar junction transistor and overcoming the reference voltage of the voltage detection shunt regulator or the voltage detection bipolar junction transistor, by illuminating the external LED sub-array The current is a second current, when the input voltage overcomes all of the forward voltage drops of the external LED sub-arrays, and overcomes the other voltage detection shunt regulator or the other voltage detection bi-carrier junction transistor When the reference voltage is not overcome, the current of the external LED sub-array that is illuminated is a third current when the reference voltage of the voltage detecting shunt regulator or the voltage detecting bipolar junction transistor is not overcome. A current is greater than the third current, and the third current is greater than the second current. The LED light engine electronic control device according to claim 9, wherein the line voltage adjustment rate compactor further comprises a voltage detection bypass switch, wherein the voltage detection bypass switch is controlled by the voltage detection in parallel The regulator or the voltage detecting bipolar junction transistor, and the channel of the voltage detection bypass switch is coupled in parallel with a portion of a voltage dividing resistor, and the voltage dividing resistor is further coupled to the current detecting resistor. When the voltage detecting shunt regulator or the voltage detecting double carrier junction transistor is turned on, the voltage detecting bypass switch is turned on to bypass the voltage dividing resistor, so that the line voltage adjusting rate tightener regulates the passage. The current of the LED sub-array is the second current. The LED light engine electronic control device of claim 13, wherein the voltage detection bypass switch is a gold oxide half field effect transistor or a photoelectric crystal. The LED light engine electronic control device of claim 1, further comprising a sinusoidal voltage compensator, the first end of the sinusoidal voltage compensator being coupled to the rectifier, the second end of the sinusoidal voltage compensator being grounded, The voltage dividing node of the sinusoidal voltage compensator is coupled to one of the comparison circuits, the DC pulse voltage having a partial pressure at a voltage dividing node of the sinusoidal voltage compensator, wherein the voltage dividing is used to provide segmentation lighting The plurality of current-sinusoidal components of the LED sub-arrays cause the waveforms of the currents that segmentally illuminate the LED sub-arrays to be closer to a sine wave. The LED light engine electronic control device of claim 1, wherein each of the bypass switches includes a depletion type MOS field effect transistor coupled to a Zener diode, a first resistor, and a second a resistor, the anode of the Zener diode is coupled to the gate of the depleted metal oxide half field effect transistor, and the cathode of the Zener diode is coupled to the source of the depleted metal oxide half field effect transistor A resistor is coupled in parallel with the Zener diode, and the second resistor is coupled to the gate of the MOS field transistor and the corresponding comparison circuit. The LED light engine electronic control device of claim 16, further comprising a further dual carrier junction transistor, wherein the second resistor is coupled to the other through the other dual carrier junction transistor Circuit. The LED light engine electronic control device of claim 1, wherein each of the bypass switches includes an enhanced MOS field effect transistor and a starting resistor, and the starting resistor is coupled to the enhanced MOS field. Between the gate and the drain of the effect transistor, the capacitance between the gate and the source of the enhanced MOS field-effect transistor is charged through the startup resistor. The LED light engine electronic control device of claim 18, further comprising a plurality of diodes, wherein the anodes of the diodes are respectively coupled to the corresponding bypass switches, and the cathodes of the diodes They are respectively coupled to the anodes of the corresponding external LED sub-arrays. The LED light engine electronic control device of claim 18, further comprising a voltage regulator, wherein the voltage regulator comprises a fourth dual carrier junction transistor, a capacitor, and another Zener diode And a third resistor, the capacitor is coupled between the emitter of the bipolar junction transistor and the anode of the other Zener diode, and the third resistor is connected to the fourth bipolar carrier Between the base and the collector of the surface transistor. For example, the LED light engine electronic control device described in claim 1 is more The plurality of flash suppression capacitors and the plurality of diodes are respectively connected in parallel to the corresponding external LED sub-array, and the cathode of each of the diodes is coupled to the anode of the corresponding external LED sub-array, so that The input voltage overcomes the sum of the forward voltage drops of the external LED sub-array below the current level and below, but does not overcome the sum of the forward voltage drops of the external LED sub-array below the upper stage and the upper stage, the input current is lit and the level is An external LED sub-array below the stage, and the flicker suppression capacitors discharge to illuminate the external LED sub-array above the level. The LED light engine electronic control device of claim 1, further comprising a plurality of flicker suppression capacitors and a plurality of diodes, wherein each of the flicker suppression capacitors is connected in parallel or in plurality of external LEDs in series An array, and each cathode of the diode is coupled to an anode of the corresponding external LED sub-array such that when the input voltage overcomes the sum of the forward voltage drops of the external LED sub-array of the current stage and below, but does not overcome the superior And the sum of the forward voltage drops of the external LED sub-array below the upper level, the input current illuminates the external LED sub-array of the current level and below, and the flicker suppression capacitors discharge to illuminate the external LEDs of the upper stage and the upper level Subarray. The LED light engine electronic control device according to claim 1, wherein the LED light engine electronic control device is implemented on an integrated circuit, or is divided into a plurality of integrated circuits by a module, and then Integrated on a circuit board.