TWI511441B - Apparatus for signal receving and method for signal receiving - Google Patents

Apparatus for signal receving and method for signal receiving Download PDF

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TWI511441B
TWI511441B TW102128321A TW102128321A TWI511441B TW I511441 B TWI511441 B TW I511441B TW 102128321 A TW102128321 A TW 102128321A TW 102128321 A TW102128321 A TW 102128321A TW I511441 B TWI511441 B TW I511441B
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signal
frequency
value
offset
digital
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TW201507344A (en
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Chih Chung Teng
Yu Cheng Liu
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Description

信號接收裝置及信號接收方法Signal receiving device and signal receiving method

本發明是有關於一種信號接收裝置及信號接收方法。The present invention relates to a signal receiving apparatus and a signal receiving method.

一般而言,傳送機與接收機之本地振盪器不同步時會引發載波頻率偏移(carrier frequency offset,CFO)以及載波相位差(phase error)等信號失真之現象。在目前常見的多載波(multi-carrier)的發射接收系統中,信號多以正交分頻多工(Orthogonal Frequency Division Multiplexing,OFDM)作調變,此時接收端需從同相路徑(In-phase path)以及正交路徑(Quadrature path)收下複數信號,透過快速傅立葉轉換(Fast Fourier Transform,FFT)將時域信號轉為頻域信號再進行相關解調程序。於是,接收端可藉由分析複數信號,估得信號的強度及相位,進一步補償上述的載波頻率偏移以及相位差。In general, when the transmitter and the local oscillator of the receiver are not synchronized, signal distortion such as carrier frequency offset (CFO) and carrier phase error may be caused. In the current multi-carrier transmission and reception system, the signals are mostly modulated by Orthogonal Frequency Division Multiplexing (OFDM), and the receiving end needs to be from the in-phase path (In-phase). Path) and the quadrature path receive the complex signal, and the time domain signal is converted into the frequency domain signal by the Fast Fourier Transform (FFT) and then the correlation demodulation process is performed. Therefore, the receiving end can further compensate the above-mentioned carrier frequency offset and phase difference by analyzing the complex signal to estimate the strength and phase of the signal.

相反地,在單載波(single-carrier)的發射接收系統中,接收二位元相位偏移調變(Binary Phase Shift Keying,BPSK)的 信號時,接收端僅需要搭載簡單的解調變器以及相關處理電路,理想上,即可得到信號所承載的資料內容,無須運用快速傅立葉轉換(Fast Fourier Transform,FFT)電路,也無須外加複數解調的專用電路。此類接收機相較於其他接收系統而言具有複雜度較低的優勢。然而,載波頻率偏移的估測以及相位差的補償則因為相位資訊的缺乏成了棘手問題。Conversely, in a single-carrier transmit and receive system, receive Binary Phase Shift Keying (BPSK) When the signal is used, the receiving end only needs to carry a simple demodulation transformer and related processing circuit. Ideally, the data content carried by the signal can be obtained without using a Fast Fourier Transform (FFT) circuit, and there is no need to add a complex number. Dedicated circuit for demodulation. Such receivers have the advantage of being less complex than other receiving systems. However, the estimation of the carrier frequency offset and the compensation of the phase difference become a thorny problem because of the lack of phase information.

本發明提出一種信號接收裝置以及信號接收方法,用於接收二位元相位偏移調變(Binary Phase Shift Keying,BPSK)的單載波實數信號,以及補償載波頻率偏移以及相位差所造成的問題。The present invention provides a signal receiving apparatus and a signal receiving method for receiving a single-carrier real number signal of Binary Phase Shift Keying (BPSK), and compensating for problems caused by carrier frequency offset and phase difference. .

本發明的一種信號接收裝置,適用於接收一單載波(single carrier)實數信號,其中該單載波實數信號以一二位元相位偏移調變(Binary Phase Shift Keying,BPSK)方式調變而成,包括:一射頻電路、一類比/數位轉換器、一降頻單元以及一基頻處理電路。射頻電路接收單載波實數信號。類比/數位轉換器耦接射頻電路,接收單載波實數信號並轉換為一數位中頻實數信號,其中數位中頻實數信號位於一中頻頻率。降頻單元,耦接類比/數位轉換器,根據一同步信號轉換數位中頻實數信號為一基頻信號,其中同步信號位於一本地中頻頻率。基頻處理電路耦接降頻單元,接收基頻信號並處理基頻信號以得到一數位資料。其中, 降頻單元執行一載波頻率偏移估測暨補償演算法,估測中頻頻率的一偏移頻率值,並根據偏移頻率值調整本地中頻頻率的頻率值,以補償數位中頻實數信號與該基頻信號之間的轉換。以及,降頻單元執行一載波相位差修正演算法,動態調整偏移頻率值,以修正中頻實數信號與同步信號中的一相位差。A signal receiving apparatus of the present invention is adapted to receive a single carrier real number signal, wherein the single carrier real number signal is modulated by a Binary Phase Shift Keying (BPSK) modulation method. The method includes: a radio frequency circuit, a analog/digital converter, a frequency down unit, and a base frequency processing circuit. The radio frequency circuit receives a single carrier real number signal. The analog/digital converter is coupled to the RF circuit, receives the single carrier real number signal and converts it into a digital intermediate frequency real number signal, wherein the digital intermediate frequency real number signal is located at an intermediate frequency. The frequency down unit is coupled to the analog/digital converter, and converts the digital intermediate frequency real signal into a fundamental frequency signal according to a synchronization signal, wherein the synchronization signal is located at a local intermediate frequency. The baseband processing circuit is coupled to the down-converting unit, receives the baseband signal and processes the baseband signal to obtain a digital data. among them, The frequency reduction unit performs a carrier frequency offset estimation and compensation algorithm, estimates an offset frequency value of the intermediate frequency, and adjusts the frequency value of the local intermediate frequency according to the offset frequency value to compensate the digital intermediate frequency real signal. Conversion with the baseband signal. And, the frequency reduction unit performs a carrier phase difference correction algorithm to dynamically adjust the offset frequency value to correct a phase difference between the intermediate frequency real signal and the synchronization signal.

本發明的信號接收方法,適用於一信號接收裝置,其中該信號接收裝置接收一單載波實數信號,其中該單載波實數信號以一二位元相位偏移調變方式調變而成,所述信號接收方法包括以下步驟。首先,接收該單載波實數信號。然後,轉換單載波實數信號為一數位中頻實數信號,其中數位中頻實數信號位於一中頻頻率。接著,根據一同步信號轉換數位中頻實數信號為一基頻信號,其中同步信號位於一本地中頻頻率。再者,執行一載波頻率頻率偏移估測暨補償演算法,估測中頻頻率的一偏移頻率值,並根據偏移頻率值調整本地中頻頻率的頻率值,以補償數位中頻實數信號與基頻信號之間的轉換。其次,執行一載波相位差修正演算法,動態調整偏移頻率值,以修正中頻實數信號與同步信號間的一相位差。以及,處理基頻信號以得到一數位資料。The signal receiving method of the present invention is applicable to a signal receiving apparatus, wherein the signal receiving apparatus receives a single carrier real number signal, wherein the single carrier real number signal is modulated by a two-bit phase offset modulation method. The signal receiving method includes the following steps. First, the single carrier real number signal is received. Then, the converted single carrier real number signal is a digital intermediate frequency real number signal, wherein the digital intermediate frequency real number signal is located at an intermediate frequency. Then, the digital intermediate frequency real signal is converted into a fundamental frequency signal according to a synchronization signal, wherein the synchronization signal is located at a local intermediate frequency. Furthermore, performing a carrier frequency frequency offset estimation and compensation algorithm, estimating an offset frequency value of the intermediate frequency, and adjusting the frequency value of the local intermediate frequency according to the offset frequency value to compensate the digital intermediate frequency real number The conversion between the signal and the fundamental signal. Next, a carrier phase difference correction algorithm is performed to dynamically adjust the offset frequency value to correct a phase difference between the intermediate frequency real signal and the synchronization signal. And, processing the baseband signal to obtain a digital data.

基於上述,本發明提供一種信號接收裝置及信號接收方法,透過載波頻率偏移估測暨補償演算法以及載波相位差修正演算法來補償基頻信號上的載波頻率偏移以及載波相位差。Based on the above, the present invention provides a signal receiving apparatus and a signal receiving method for compensating for a carrier frequency offset and a carrier phase difference on a baseband signal by a carrier frequency offset estimation and compensation algorithm and a carrier phase difference correction algorithm.

為讓本發明的上述特徵和優點能更明顯易懂,下文特舉實施例,並配合所附圖式作詳細說明如下。The above described features and advantages of the invention will be apparent from the following description.

10‧‧‧信號接收裝置10‧‧‧Signal receiving device

110‧‧‧射頻電路110‧‧‧RF circuit

120‧‧‧類比/數位轉換器120‧‧‧ Analog/Digital Converter

130‧‧‧降頻單元130‧‧‧down frequency unit

131‧‧‧數值控制振盪器131‧‧‧Numerical Controlled Oscillator

132‧‧‧數位降頻轉換器132‧‧‧Digital Down Converter

133‧‧‧處理單元133‧‧‧Processing unit

1331‧‧‧高頻拒絕單元1331‧‧‧High frequency rejection unit

610‧‧‧絕對值計算器610‧‧‧Absolute Value Calculator

620‧‧‧低通濾波器620‧‧‧ low pass filter

630‧‧‧降取樣單元630‧‧Sampling unit

1332‧‧‧微分器1332‧‧‧ Differentiator

1333‧‧‧信號選擇單元1333‧‧‧Signal selection unit

710‧‧‧中繼單元710‧‧‧Relay unit

720‧‧‧否互斥或閘720‧‧‧No mutual exclusion or gate

730‧‧‧延遲單元730‧‧‧Delay unit

740‧‧‧選擇器740‧‧‧Selector

140‧‧‧基頻處理電路140‧‧‧ fundamental frequency processing circuit

R[n]‧‧‧單載波實數信號R[n]‧‧‧ single carrier real number signal

‧‧‧數位中頻實數信號 ‧‧‧Digital IF real signal

r [n ]‧‧‧基頻信號 r [ n ]‧‧‧ fundamental frequency signal

r O [n ]‧‧‧過補償基頻信號 r O [ n ]‧‧‧Overcompensated baseband signal

SS‧‧‧同步信號SS‧‧‧Synchronization signal

OSS‧‧‧過補償同步信號OSS‧‧‧Overcompensated sync signal

CS‧‧‧控制信號CS‧‧‧Control signal

RD‧‧‧殘餘低頻信號RD‧‧‧ residual low frequency signal

Z‧‧‧指示信號Z‧‧‧ indication signal

Y‧‧‧選擇信號Y‧‧‧Selection signal

Ypre ‧‧‧延遲選擇信號Y pre ‧‧‧delay selection signal

X‧‧‧數位信號X‧‧‧ digital signal

A‧‧‧資料信號的最大振幅A‧‧‧Maximum amplitude of the data signal

HS1‧‧‧第一諧波HS1‧‧‧ first harmonic

I 1 ‧‧‧第一估測區間 I 1 ‧‧‧First estimated interval

f OC ‧‧‧過補償值 f OC ‧‧‧Overcompensation value

f offset ‧‧‧偏移頻率 f offset ‧‧‧offset frequency

f MAX ‧‧‧偏移頻率的最大值 f MAX ‧‧‧Maximum offset frequency

f U ‧‧‧單位頻率值 f U ‧‧‧unit frequency value

‧‧‧目標頻率值 ‧‧‧target frequency value

f compens ‧‧‧動態估測頻率 f compens ‧‧‧dynamic estimation frequency

f const ‧‧‧頻率常值 f const ‧‧‧frequency constant

S801~S805‧‧‧步驟S801~S805‧‧‧Steps

圖1為根據本發明一實施例所繪示信號接收裝置的功能方塊圖。FIG. 1 is a functional block diagram of a signal receiving apparatus according to an embodiment of the invention.

圖2為根據本發明一實施例所繪示降頻單元的功能方塊圖。FIG. 2 is a functional block diagram of a frequency down unit according to an embodiment of the invention.

圖3A為根據本發明一實施例所繪示基頻信號的絕對值的頻譜圖。FIG. 3A is a frequency spectrum diagram showing absolute values of a fundamental frequency signal according to an embodiment of the invention.

圖3B所繪示則為根據本發明一實施例所繪示過補償基頻信號的絕對值的頻譜圖。FIG. 3B is a frequency spectrum diagram illustrating the absolute value of the compensated baseband signal according to an embodiment of the invention.

圖4A為根據本發明一實施例所繪示第一諧波與估測區間的關係圖。FIG. 4A is a diagram showing a relationship between a first harmonic and an estimated interval according to an embodiment of the invention.

圖4B為根據本發明一實施例所繪示在估測區間中第一諧波與單音信號的關係圖。FIG. 4B is a diagram showing a relationship between a first harmonic and a tone signal in an estimation interval according to an embodiment of the invention.

圖5為根據本發明一實施例所繪示處理單元的部份功能方塊圖。FIG. 5 is a partial functional block diagram of a processing unit according to an embodiment of the invention.

圖6為根據本發明一實施例所繪示高頻拒絕單元的功能方塊圖。FIG. 6 is a functional block diagram showing a high frequency reject unit according to an embodiment of the invention.

圖7為根據本發明一實施例所繪示信號選擇單元的功能方塊圖。FIG. 7 is a functional block diagram of a signal selection unit according to an embodiment of the invention.

圖8為根據本發明一實施例所繪示信號接收方法的步驟流程圖。FIG. 8 is a flow chart showing the steps of a signal receiving method according to an embodiment of the invention.

以下,則將詳細說明本發明如何分析一個以BPSK調變的單載波實數信號,進一步提出載波頻率偏移補償及載波相位差消除的方法。Hereinafter, a detailed description will be given of how the present invention analyzes a single-carrier real number signal modulated by BPSK, and further proposes a method of carrier frequency offset compensation and carrier phase difference cancellation.

圖1為根據本發明一實施例所繪示信號接收裝置的功能方塊圖。其中在本實施例中,信號接收裝置10用於接收BPSK調變的單載波實數信號。請參照圖1,信號接收裝置10包括射頻電路110、類比/數位轉換器120、降頻單元130以及基頻處理電路140。射頻電路110接收單載波實數信號R(t)。類比/數位轉換器120耦接射頻電路110,接收單載波實數信號R(t)並將單載波實數信號R(t)轉換為數位中頻實數信號,其中數位中頻實數信號位於已知的一中頻頻率(intermediate frequency)。降頻單元130耦接類比/數位轉換器120,根據同步信號將數位中頻實數信號轉換為基頻信號r [n ],其中同步信號位於一本地中頻頻率。基頻處理電路140耦接降頻單元130,接收基頻信號r [n ]並處理基頻信號r [n ]以得到數位資料,也就是單載波實數信號R[n]中所承載的資料內容。FIG. 1 is a functional block diagram of a signal receiving apparatus according to an embodiment of the invention. In the present embodiment, the signal receiving apparatus 10 is configured to receive a BPSK modulated single carrier real number signal. Referring to FIG. 1, the signal receiving apparatus 10 includes a radio frequency circuit 110, an analog/digital converter 120, a down-converting unit 130, and a baseband processing circuit 140. The radio frequency circuit 110 receives a single carrier real number signal R(t). The analog/digital converter 120 is coupled to the radio frequency circuit 110, receives the single carrier real number signal R(t) and converts the single carrier real number signal R(t) into a digital intermediate frequency real number signal. Digital IF real number signal Located at a known intermediate frequency. The down-converting unit 130 is coupled to the analog/digital converter 120 and converts the digital intermediate frequency real signal according to the synchronization signal. Converted to a baseband signal r [ n ], where the sync signal is at a local intermediate frequency. The baseband processing circuit 140 is coupled to the frequency down unit 130, receives the baseband signal r [ n ], and processes the baseband signal r [ n ] to obtain digital data, that is, the data content carried in the single carrier real number signal R[n]. .

其中,降頻單元130執行一載波頻率偏移估測暨補償演算法,估測數位中頻實數信號位於之中頻頻率的一偏移頻率值,並根據偏移頻率值調整本地中頻頻率的頻率值,以補償數位中頻實數信號與基頻信號r [n ]之間的轉換。以及降頻單元 130執行一載波相位差修正演算法,動態調整偏移頻率值,以修正中頻實數信號與同步信號中的一相位差。以下則將以實施例及圖式詳細說明上述的載波頻率偏移補償演算法以及載波相位差消除演算法的實施內容。The frequency down unit 130 performs a carrier frequency offset estimation and compensation algorithm to estimate the digital intermediate frequency real number signal. An offset frequency value at the intermediate frequency, and adjusting the frequency value of the local intermediate frequency according to the offset frequency value to compensate the digital intermediate frequency real signal Conversion with the baseband signal r [ n ]. And the frequency down unit 130 performs a carrier phase difference correction algorithm to dynamically adjust the offset frequency value to correct the intermediate frequency real number signal A phase difference from the sync signal. Hereinafter, the implementation of the carrier frequency offset compensation algorithm and the carrier phase difference cancellation algorithm described above will be described in detail by way of embodiments and drawings.

圖2為本發明一實施例所對應的降頻單元的功能方塊圖。請參照圖1及圖2,降頻單元130包括數值控制振盪器131、數位降頻轉換器(Digital Down Converter,DDC)132以及處理單元133。數值控制振盪器131產生同步信號SS,其中同步信號位於一本地中頻頻率。數位降頻轉換器132耦接類比/數位轉換器120以及數值控制振盪器131,根據同步信號SS轉換數位中頻實數信號為基頻信號r [n ]。處理單元133耦接數位降頻轉換器132及數值控制振盪器131,傳送控制信號CS至數值控制振盪器131,其中控制信號CS中包括預先定義的一本地中頻頻率的頻率值與一動態估測頻率值之和(即,修正後的中頻頻率值)。其中,預先定義的本地中頻頻率的頻率值即為本地頻率的預期頻率值,而偏移頻率值即為透過載波頻率偏移估測暨補償演算法所得到,並由透過載波相位差修正演算法動態調整偏移頻率值。2 is a functional block diagram of a frequency down unit corresponding to an embodiment of the present invention. Referring to FIGS. 1 and 2 , the down-converting unit 130 includes a numerically controlled oscillator 131 , a digital down converter (DDC) 132 , and a processing unit 133 . The numerically controlled oscillator 131 produces a synchronization signal SS, wherein the synchronization signal is located at a local intermediate frequency. The digital down converter 132 is coupled to the analog/digital converter 120 and the numerically controlled oscillator 131, and converts the digital intermediate frequency real signal according to the synchronization signal SS. Is the fundamental frequency signal r [ n ]. The processing unit 133 is coupled to the digital down converter 132 and the numerically controlled oscillator 131, and transmits the control signal CS to the numerically controlled oscillator 131. The control signal CS includes a predefined frequency value of a local intermediate frequency and a dynamic estimation. The sum of the measured frequency values (ie, the corrected intermediate frequency value). The frequency value of the predefined local intermediate frequency is the expected frequency value of the local frequency, and the offset frequency value is obtained by the carrier frequency offset estimation and compensation algorithm, and is corrected by the carrier phase difference correction algorithm. The method dynamically adjusts the offset frequency value.

其中,當數值控制振盪器131接收控制信號CS,數值控制振盪器調整同步信號SS之頻率值到控制信號CS所指示之頻率值(即,預先定義的一本地中頻頻率的頻率值與一動態估測頻率值之和)。Wherein, when the numerically controlled oscillator 131 receives the control signal CS, the numerically controlled oscillator adjusts the frequency value of the synchronization signal SS to the frequency value indicated by the control signal CS (ie, a predefined frequency value of a local intermediate frequency and a dynamic Estimate the sum of the frequency values).

理想的情況是,預先定義的中頻頻率值與數位中頻實數 信號所位於的中頻頻率的頻率值相同(即偏移頻率值為零)。如此一來,數位降頻轉換器132便能利用同步信號SS成功鎖定數位中頻實數信號,而產生信號品質良好的基頻信號r [n ]。然而,由於信號傳送端與信號接收裝置10之間往往具有些微的差距,而此差距即為上述載波頻率偏移(即,偏移頻率值不等於0)的問題。Ideally, a predefined IF frequency value and a digital IF real signal The frequency of the intermediate frequency is located at the same value (ie, the offset frequency value is zero). In this way, the digital down converter 132 can successfully lock the digital intermediate frequency real signal by using the synchronization signal SS. And generate a fundamental signal r [ n ] with good signal quality. However, since there is often a slight gap between the signal transmitting end and the signal receiving device 10, the difference is the above-mentioned carrier frequency offset (that is, the offset frequency value is not equal to 0).

在此,基頻信號表示如下式(1):r [n ]=m [n ]×cos(2πf offset T s n +θ offset ),where|m[n]|=|Acos(2πf BPSK T s n )| (1)其中m[n]表示為基頻信號所承載的資料信號,也就是若是當沒有載波頻率偏移的情況發生時,基頻信號r [n ]便會等於資料信號m[n]。A為資料信號m[n]的最大振幅,而f BPSK 即為資料信號m[n]中的資料頻率,也就是BPSK的資料頻率。在式(1)中的後項即為載波頻率偏移以及相位差所造成的誤差項,f offset 為偏移頻率,而θ offset 則表示為相位差。由於資料信號m[n]的資料頻率f BPSK 的頻率值遠大於偏移頻率f offset 的頻率值,上式(1)所示之基頻信號r[n] 如同資料信號m[n]被後項cos(2πf offset T s n +θ offset )所包絡(envelope),造成資料信號m[n]的振幅強度受到偏移頻率f offset 的控制而大小不定,甚至亦可能有相位反轉的狀況出現。這樣的情況,則造成後端基頻處理電路140在處理基頻信號r[n] 時,難以正確的判斷資料信號m[n]的資料內容。Here, the fundamental frequency signal represents the following equation (1): r [ n ]= m [ n ]×cos(2 πf offset T s n + θ offset ), where|m[n]|=|Acos(2 πf BPSK T s n )| (1) where m[n] represents the data signal carried by the fundamental frequency signal, that is, if there is no carrier frequency offset, the fundamental frequency signal r [ n ] will be equal to the data signal m[n]. A is the maximum amplitude of the data signal m[n], and f BPSK is the data frequency in the data signal m[n], which is the data frequency of BPSK. The latter term in equation (1) is the error term caused by the carrier frequency offset and the phase difference, f offset is the offset frequency, and θ offset is expressed as the phase difference. Since the frequency value of the data frequency f BPSK of the data signal m[n] is much larger than the frequency value of the offset frequency f offset , the fundamental frequency signal r[n] shown in the above equation (1) is like the data signal m[n] The envelope of cos(2πf offset T s n + θ offset ) envelops, so that the amplitude intensity of the data signal m[n] is controlled by the offset frequency f offset and the magnitude is variable, and even the phase inversion may occur. . In this case, it is difficult for the back-end baseband processing circuit 140 to correctly determine the data content of the data signal m[n] when processing the baseband signal r[n] .

而在本發明中,為了要消除上述載波頻率偏移以及相位差所造成的影響,則利用了載波頻率偏移估測暨補償演算法估測 實數中頻信號之包絡線的頻率值f offset (即前級之中頻頻率的偏移量),將偏移頻率值f offset 降至最低後,再透過載波相位差修正演算法動態地補償相位差,以便提升信號r[n] 的信號強度。其中,為了避免資料信號m[n]中的資料對估測的內容造成不當的影響,以下的估測多以基頻信號的絕對值|r[n] |來進行計算。而在資料頻率f BPSK 的頻率值遠大於偏移頻率f offset 的頻率值(即,偏移頻率值)的前提下,基頻信號的絕對值|r[n] |可利用泰勒展開式(Taylor expansion)展開式(1)如下: 其中|r H [n] |則表示頻率不小於資料頻率f BPSK 之所有高頻項的總和。In the present invention, in order to eliminate the influence of the carrier frequency offset and the phase difference, the carrier frequency offset estimation and compensation algorithm is used to estimate the real IF signal. The frequency value f offset of the envelope (ie, the offset of the intermediate frequency of the previous stage), after the offset frequency value f offset is minimized, the carrier phase difference correction algorithm dynamically compensates the phase difference to improve The signal strength of the signal r[n] . Among them, in order to avoid the undue influence of the data in the data signal m[n] on the estimated content, the following estimation is mostly calculated by the absolute value of the fundamental frequency signal | r[n] | On the premise that the frequency value of the data frequency f BPSK is much larger than the frequency value of the offset frequency f offset (ie, the offset frequency value), the absolute value of the fundamental frequency signal | r[n] | can be exploited by Taylor expansion (Taylor) Expansion) (1) is as follows: Where | r H [n] | indicates that the frequency is not less than the sum of all high frequency terms of the data frequency f BPSK .

載波頻率偏移估測暨補償演算法說明如下。首先處理單元133設定一過補償頻率值為預先定義的中頻頻率值與過補償值f OC 之和,並傳送包括過補償頻率值的控制信號CS至數值控制振盪器131。然後,當數值控制振盪器131接收控制信號CS時,根據過補償頻率值產生過補償同步信號OSS,並傳送過補償同步信號OSS至數位降頻轉換器132。數位降頻轉換器132接收過補償同步信號OSS時,數位降頻轉換器132根據過補償同步信號OSS中的過補償頻率值產生過補償基頻信號r O [n] 。以及,處理單元133根據過補償基頻信號r O [n] 得到偏移頻率的頻率值。The carrier frequency offset estimation and compensation algorithm is described below. First, the processing unit 133 sets an overcompensated frequency value to the sum of the predefined intermediate frequency value and the overcompensated value f OC , and transmits a control signal CS including the overcompensated frequency value to the numerically controlled oscillator 131. Then, when the numerically controlled oscillator 131 receives the control signal CS, the overcompensated synchronizing signal OSS is generated based on the overcompensated frequency value, and the compensated synchronizing signal OSS is transmitted to the digital down converter 132. When the digital down converter 132 receives the compensated synchronization signal OSS, the digital down converter 132 generates an overcompensated base frequency signal r O [n] according to the overcompensated frequency value in the overcompensated synchronization signal OSS. And, the processing unit 133 obtains the frequency value of the offset frequency based on the overcompensated baseband signal r O [n] .

過補償信號r O [n] 的優點在於,相較於基頻信號的絕對值|r[n] |的頻譜,過補償基頻信號的絕對值|r O [n] |的頻譜之中,各個諧波之 間距離較大,於是處理單元133將更容易鎖定過補償基頻信號的絕對值|r O [n] |頻譜中的各諧波,而不會因為諧波之間的距離過小而產生誤判。The advantage of the overcompensated signal r O [n] is that, compared to the spectrum of the absolute value | r[n] | of the fundamental frequency signal, the absolute value of the overcompensated fundamental frequency signal | r O [n] | The distance between the individual harmonics is large, so the processing unit 133 will more easily lock the absolute value of the compensated fundamental frequency signal | r O [n] | each harmonic in the spectrum, without the distance between the harmonics being too small And misjudged.

圖3A為本發明一實施例所繪示之基頻信號的絕對值|r[n] |的頻譜圖,而圖3B為根據本發明一實施例所繪示之過補償基頻信號的絕對值|r O [n] |的頻譜圖。同時參照圖3A及圖3B可發現,圖3B所示過補償基頻信號的絕對值中的所有諧波之間的距離皆被拉寬至過補償值f OC 加上偏移頻率f offset 的兩倍的距離。3A is a frequency spectrum diagram of an absolute value | r[n] | of a baseband signal according to an embodiment of the present invention, and FIG. 3B is an absolute value of an overcompensated baseband signal according to an embodiment of the invention. | Spectrogram of r O [n] | 3A and 3B, it can be found that the distance between all the harmonics in the absolute value of the overcompensated baseband signal shown in FIG. 3B is widened to the overcompensation value f OC plus the offset frequency f offset Double the distance.

處理單元133則針對諧波之一設定一個估測區間,並在該區間中尋找此諧波的頻率值為何,當此諧波的頻率值已知,則可透過此諧波的頻率值得到偏移頻率值(即,估算得到的偏移頻率的頻率值)。例如如圖3B所示實施例中,處理單元133針對第一諧波HS1設定了估測區間,而圖3B所示頻譜上,第一諧波HS1的頻率值即為過補償值f OC 加上偏移頻率f offset 的兩倍。在過補償值f OC 已知的情況下,在得到第一諧波HS1的頻率值後便可使用第一諧波HS1的頻率值計算得到偏移頻率值The processing unit 133 sets an estimation interval for one of the harmonics, and finds the frequency value of the harmonic in the interval. When the frequency value of the harmonic is known, the frequency value of the harmonic can be obtained. Shift frequency value (ie, the estimated frequency value of the offset frequency). For example, in the embodiment shown in FIG. 3B, the processing unit 133 sets an estimation interval for the first harmonic HS1, and the frequency value of the first harmonic HS1 in the spectrum shown in FIG. 3B is the overcompensation value f OC plus The offset frequency f offset is twice. In the case where the over-compensation value f OC is known, the offset frequency value can be calculated using the frequency value of the first harmonic HS1 after obtaining the frequency value of the first harmonic HS1. .

過補償值f OC 必須夠大,以使得第一諧波與第二諧波的估測區間不重疊。若設定偏移頻率f offset 的最大值為f MAX ,而使得兩個鄰近的估測區間不能互相重疊的關係式為: The overcompensation value f OC must be large enough so that the estimated intervals of the first harmonic and the second harmonic do not overlap. If the maximum value of the offset frequency f offset is set to f MAX , the relationship that the two adjacent estimation intervals cannot overlap each other is:

由式(3)便可計算得到過補償值f OC 必須大於等於3倍的偏移頻率最大值f MAX 。而各個諧波的估測區間則為:I m =[2m (f OC -f MAX ),2m (f OC +f MAX )] (4)From equation (3), it is calculated that the overcompensated value f OC must be greater than or equal to three times the offset frequency maximum value f MAX . The estimated interval for each harmonic is: I m =[2 m ( f OC - f MAX ), 2 m ( f OC + f MAX )] (4)

例如,圖4A為根據本發明一實施例所繪示第一諧波與估測區間的關係圖。請參照圖4A,對應於第一諧波HS1的估測區間I 1 即介於2(f OC -f MAX )與2(f OC +f MAX )之間。在本實施例中,處理單元133即以估測區間I 1 估測對應於第一諧波HS1的頻率值,並藉此獲得偏移頻率f offset For example, FIG. 4A is a diagram showing a relationship between a first harmonic and an estimated interval according to an embodiment of the invention. Referring to FIG. 4A, the estimated interval I 1 corresponding to the first harmonic HS1 is between 2 ( f OC - f MAX ) and 2 ( f OC + f MAX ). In the present embodiment, i.e., the processing unit 133 to estimate the interval I 1 corresponding to the first harmonic frequency estimation value HS1 and thereby obtain an offset frequency f offset.

圖4B為根據本發明一實施例所繪示在估測區間中第一諧波與單音信號的關係圖。在本實施例中,處理單元133在估測區間I 1 中擺放多個單音(single tone)信號f k 。其中,單音信號f k 平均分佈於估測區間I 1 中,彼此間隔兩倍的單位頻率值2f U 。單位頻率值f U 的選擇將影響估測偏移頻率的頻率值的精準度。k值介於0到K,即為單音信號f k 的索引值,K值則對應於單音信號f k 的數量。所以,當處理單元133接收過補償基頻信號r O [n] 時,處理單元133對過補償基頻信號r O [n] 取絕對值。接著,處理單元133計算過補償基頻信號的絕對值|r O [n] |與這些單音信號f k 之間的多個相關值(correlation)。FIG. 4B is a diagram showing a relationship between a first harmonic and a tone signal in an estimation interval according to an embodiment of the invention. In the present embodiment, the processing unit 133 places a plurality of single tone signals f k in the estimation interval I 1 . Wherein, the tone signals f k are evenly distributed in the estimation interval I 1 , and are separated from each other by twice the unit frequency value 2 f U . The selection of the unit frequency value f U will affect the accuracy of the frequency value at which the offset frequency is estimated. The value of k is between 0 and K, which is the index value of the tone signal f k , and the value of K corresponds to the number of tone signals f k . Therefore, when the processing unit 133 receives the compensated baseband signal r O [n] , the processing unit 133 takes the absolute value of the overcompensated baseband signal r O [n] . Next, the processing unit 133 calculates a plurality of correlation values between the absolute value | r O [n] | of the compensated baseband signal and the tone signals f k .

其中,單音信號f k 分別具有餘弦子信號i[n,k] 以及正弦子信號q[n,k] 。而距離第一諧波HS1最接近的單音信號f k 之索引值則可以可被表示為: Among them, the tone signal f k has a cosine sub-signal i[n, k] and a sine sub-signal q[n, k], respectively . The index value of the tone signal f k closest to the first harmonic HS1 Then can be expressed as:

其中為單音信號f k 的餘弦子信號i [n ,k ]與第一諧波HS1的相關值,可被表示為: among them The correlation value of the cosine sub-signal i [ n , k ] of the tone signal f k and the first harmonic HS1 can be expressed as:

為單音信號f k 的正弦子信號q [n ,k ]與第一諧波HS1的相關值,可被表示為: The correlation value of the sinusoidal signal q [ n , k ] of the tone signal f k and the first harmonic HS1 can be expressed as:

其中N為取樣點的數量。值得注意的是,上述相關值的計算可運用合角公式節省儲存各個暫存單音信號的記憶體。例如,在不使用合角公式計算式(5)的內容時,處理單元133需要2*N*(K+1)大小的暫存記憶體,而使用合角公式計算式(5)的內容時,則僅需2*(K+1)大小的暫存記憶體即可。Where N is the number of sampling points. It is worth noting that the above correlation values can be calculated by using the angle formula to save the memory for storing each temporary tone signal. For example, when the content of the equation (5) is not calculated using the angle formula, the processing unit 133 requires a temporary memory of 2*N*(K+1) size, and when the content of the equation (5) is calculated using the angle formula, , you only need 2*(K+1) size of scratch memory.

處理單元133求出式(5)中的最大相關值的索引值(其中,),而所對應的單音信號頻率為。處理單元133並根據目標頻率值產生估測頻率值。目標頻率值可被表示為: The processing unit 133 finds an index value of the maximum correlation value in the equation (5) (among them, ),and The corresponding tone signal frequency is . Processing unit 133 and according to the target frequency value The estimated frequency value is generated. Target frequency value Can be expressed as:

當得到目標頻率值後,便可推得偏移頻率為: When the target frequency value is obtained After that, the offset frequency can be derived as:

得到偏移頻率,處理單元133便可將偏移頻率的頻率值與預先定義的中頻頻率相加而得到修正後的本地中頻頻率值,然後透過控制信號CS傳送此本地中頻頻率值至數值控制振盪器131。值得注意的是,由圖4B可以觀察到,由於單位頻率值f U 的選擇等原因,可能造成目標頻率值與第一諧波HS1的頻率值 實際上仍有些微的一些差距,使得偏移頻率仍有些許不準確。因此,本發明則另行運用載波相位差修正演算法來縮小上述的差距,或相位差所造成的影響。Get the offset frequency The processing unit 133 can shift the frequency The frequency value is added to the predefined intermediate frequency to obtain the corrected local intermediate frequency value, and then the local intermediate frequency value is transmitted to the numerically controlled oscillator 131 via the control signal CS. It is worth noting that it can be observed from Fig. 4B that the target frequency value may be caused due to the selection of the unit frequency value f U and the like. The frequency value of the first harmonic HS1 is still slightly slightly different, making the offset frequency Still a little inaccurate. Therefore, in the present invention, the carrier phase difference correction algorithm is additionally used to reduce the above-mentioned difference or the influence of the phase difference.

圖5為根據本發明一實施例所繪示處理單元的部份功能方塊圖。請參照圖5,在本實施例中,處理單元133包括高頻拒絕單元1331、耦接該高頻信號消除單元1331的微分器1332以及耦接微分器1332的信號選擇單元1333。FIG. 5 is a partial functional block diagram of a processing unit according to an embodiment of the invention. Referring to FIG. 5, in the embodiment, the processing unit 133 includes a high frequency reject unit 1331, a differentiator 1332 coupled to the high frequency signal canceling unit 1331, and a signal selecting unit 1333 coupled to the differentiator 1332.

在本發明中,載波相位差修正演算法的運作概念相似於鎖相迴路(Phase Lock Loop,PLL)的運作原理,包括以下的動作。首先,高頻拒絕單元1331持續從數位降頻轉換器132接收基頻信號r [n ],並濾除基頻信號r [n ]中的一高頻成份得到殘餘低頻信號RD。接著,微分器1332從高頻拒絕單元1331接收殘餘低頻信號RD,並微分基頻信號RD而得到指示信號Z。指示信號Z用以指示於殘餘低頻信號RD目前的取樣點時的斜率,也就是取得當下殘餘低頻信號RD處於遞增或是遞減的狀態。然後,信號選擇單元1333接收指示信號Z,並根據指示信號Z產生動態估測頻率f compens ,使得處理單元133可根據動態估測頻率f compens 的頻率值調整該估測頻率值。In the present invention, the operational concept of the carrier phase difference correction algorithm is similar to the operation principle of a phase lock loop (PLL), including the following actions. First, the high frequency rejecting unit 1331 continues to receive the fundamental frequency signal r [ n ] from the digital down converter 132, and filters out a high frequency component of the fundamental frequency signal r [ n ] to obtain a residual low frequency signal RD. Next, the differentiator 1332 receives the residual low frequency signal RD from the high frequency rejecting unit 1331, and differentiates the fundamental frequency signal RD to obtain the indication signal Z. The indication signal Z is used to indicate the slope of the current sampling point of the residual low frequency signal RD, that is, to obtain the state in which the current residual low frequency signal RD is increasing or decreasing. Then, the signal selection unit 1333 receives the indication signal Z, Z and frequency f compens generating a dynamic estimation instruction signal, so that the processing unit 133 may be adjusted according to the estimated frequency value a frequency value of the dynamic estimation of the frequency f compens.

圖6為根據本發明一實施例所繪示高頻拒絕單元的功能方塊圖,提供圖5所示實施例中高頻拒絕單元1331的一種實施方式。請參照圖6,高頻拒絕單元1331包括絕對值計算器610、低通濾波器(low pass filter,LPF)620以及降取樣(down sample) 單元630。絕對值計算器610接收基頻信號r[n] ,計算得到基頻信號的絕對值|r[n] |,至於在本實施例中對基頻信號r[n] 取絕對值的目的為去除資料信號m[n]對估測的影響,與前述實施例相同。FIG. 6 is a functional block diagram showing a high frequency reject unit according to an embodiment of the invention, and an embodiment of the high frequency reject unit 1331 in the embodiment shown in FIG. 5 is provided. Referring to FIG. 6, the high frequency reject unit 1331 includes an absolute value calculator 610, a low pass filter (LPF) 620, and a down sample unit 630. The absolute value calculator 610 receives the fundamental frequency signal r[n] and calculates the absolute value of the fundamental frequency signal | r[n] |, and the purpose of taking the absolute value of the fundamental frequency signal r[n] in the present embodiment is to remove The influence of the data signal m[n] on the estimation is the same as in the previous embodiment.

低通濾波器620耦接絕對值計算器610,接收基頻信號的絕對值|r[n] |,濾除基頻信號的絕對值|r[n] |的高頻成份,也就是式(2)中的高頻項|r H [n] |。因此,對於低通濾波器620則包括如下式(10)的要求: The low-pass filter 620 is coupled to the absolute value calculator 610, and receives the absolute value of the fundamental frequency signal | r[n] |, and filters out the high-frequency component of the absolute value of the fundamental frequency signal | r[n] | 2) High frequency term | r H [n] |. Therefore, for the low pass filter 620, the requirements of the following formula (10) are included:

降取樣單元630,耦接低通濾波器620,接收基頻信號的絕對值|r [n ]|,並降取樣基頻信號的絕對值|r [n ]|得到殘餘低頻信號RD。降取樣的意義在於可以減少殘餘低頻信號RD中的取樣點,使得信號選擇單元1333的工作頻率可以下降,降低成本。另外,降取樣的動作兼具了低通濾波的功能。The down sampling unit 630 is coupled to the low pass filter 620, receives the absolute value of the fundamental frequency signal | r [ n ]|, and downsamples the absolute value of the fundamental frequency signal | r [ n ]| to obtain the residual low frequency signal RD. The significance of downsampling is that the sampling points in the residual low frequency signal RD can be reduced, so that the operating frequency of the signal selecting unit 1333 can be lowered, and the cost can be reduced. In addition, the downsampling action has the function of low-pass filtering.

圖7為根據本發明一實施例所繪示信號選擇單元的功能方塊圖。請參照圖7,信號選擇單元1333包括中繼(relay)單元710、否互斥或閘(NXOR gate)720,延遲單元730以及選擇器740。中繼單元710接收指示信號Z,並轉換指示信號Z為數位信號X。如先前提到的,指示信號Z之值代表當下的殘餘低頻信號RD處於遞增或是遞減的狀態,中繼單元710則進一步的將遞增或遞減的狀態轉換以二位元的方式表示,其中中繼單元710的輸入信號(指示信號Z)與輸出信號(數位信號X)的關係如下表所示。FIG. 7 is a functional block diagram of a signal selection unit according to an embodiment of the invention. Referring to FIG. 7, the signal selection unit 1333 includes a relay unit 710, a NXOR gate 720, a delay unit 730, and a selector 740. The relay unit 710 receives the indication signal Z and converts the indication signal Z into a digital signal X. As previously mentioned, the value of the indication signal Z represents that the current residual low frequency signal RD is in an incrementing or decrementing state, and the relay unit 710 further converts the incremental or decreasing state transition in a two-bit manner, wherein The relationship between the input signal (indication signal Z) of the relay unit 710 and the output signal (digital signal X) is as shown in the following table.

也就是說,當指示信號Z之值為正,表示當下的殘餘低頻信號RD處於遞增狀態,中繼單元710輸出1。而當指示信號Z之值為負,表示當下的殘餘低頻信號RD處於遞減狀態,中繼單元710輸出0。That is to say, when the value of the indication signal Z is positive, indicating that the current residual low frequency signal RD is in an increasing state, the relay unit 710 outputs 1. When the value of the indication signal Z is negative, indicating that the current residual low frequency signal RD is in a decreasing state, the relay unit 710 outputs 0.

否互斥或閘720具有第一輸入端、第二輸入端以及輸出端,其中第一輸入端耦接中繼單元710並接收數位信號X,第二輸入端耦接延遲單元730,而輸出端輸出選擇信號Y。延遲單元730則,耦接於否互斥或閘720的第二輸入端與輸出端之間,延遲選擇信號Y為延遲選擇信號Ypre ,並傳送延遲選擇信號Ypre 至否互斥或閘720的第二輸入端。The multiplexer or gate 720 has a first input end, a second input end, and an output end, wherein the first input end is coupled to the relay unit 710 and receives the digital signal X, the second input end is coupled to the delay unit 730, and the output end is coupled to the delay unit 730. The selection signal Y is output. The delay unit 730 is coupled between the second input end and the output end of the mutex or the 720, the delay selection signal Y is the delay selection signal Y pre , and the delay selection signal Y pre is transmitted to the mutex or the gate 720 The second input.

簡單的說,否互斥或閘720根據數位信號X以及前一時間點的選擇信號,也就是延遲選擇信號Ypre 來輸出選擇信號Y。否互斥或閘720的真值表如下表2所示: Briefly, the mutex or gate 720 outputs the selection signal Y based on the digital signal X and the selection signal of the previous time point, that is, the delay selection signal Y pre . The table of truth values for mutual exclusion or gate 720 is shown in Table 2 below:

選擇器740,耦接否互斥或閘720的輸出端,根據選擇信號Y以輸出動態估測頻率值f compens 。在本實施例中,當選擇信號Y等於1時,選擇器740輸出偏移頻率與頻率常值f const 的和作為動態估測頻率值f compens 或偏移頻率與頻率常值f const 的差輸出為動態估測頻率值f compens 。在得到動態估測頻率值f compens 後,處理單元133便可將動態估測頻率值f compens 與預先定義的中頻頻率值相加而得到修正後的本地中頻頻率值,並透過控制信號CS將修正後的本地中頻頻率值傳至數值控制振盪器131。The selector 740 is coupled to the output of the mutex or gate 720, and outputs a dynamic estimated frequency value f compens according to the selection signal Y. In the present embodiment, when the selection signal Y is equal to 1, the selector 740 outputs the offset frequency. The sum of the frequency constant f const as the dynamic estimated frequency value f compens or offset frequency The difference output with the frequency constant f const is the dynamic estimated frequency value f compens . After obtaining the dynamic estimated frequency value f compens , the processing unit 133 may add the dynamic estimated frequency value f compens to the predefined intermediate frequency frequency value to obtain the corrected local intermediate frequency frequency value, and transmit the control signal CS. The corrected local intermediate frequency value is passed to the numerically controlled oscillator 131.

因此,參考上述表2,當當下的基頻直流信號RD處於遞因此,參考上述表2,當當下的殘餘低頻信號RD處於遞減狀態(數位信號X為0),而前一個時間點輸出偏移頻率與頻率常值f const 的和(Ypre 為0)時,信號選擇單元1333持續輸出偏移頻率與頻率常值f const 的差(Y為1)。當當下的殘餘低頻信號RD處於遞增狀態(數位信號X為1),而前一個時間點輸出偏移頻率的負值與頻率常值f const 的差(Ypre 為1)時,信號選擇單元1333則同樣輸出偏移頻率的負值與頻率常值f const 的差(Y為1)。Therefore, referring to Table 2 above, when the current fundamental frequency DC signal RD is in progress, referring to Table 2 above, when the current residual low frequency signal RD is in a decreasing state (digital signal X is 0), and the previous time point output offset frequency When the sum of the frequency constant f const (Y pre is 0), the signal selecting unit 1333 continuously outputs the offset frequency The difference from the frequency constant f const (Y is 1). When the current residual low frequency signal RD is in an increasing state (the digital signal X is 1), and the previous time point outputs the offset frequency When the difference between the negative value and the frequency constant value f const (Y pre is 1), the signal selecting unit 1333 also outputs the offset frequency. The difference between the negative value and the frequency constant f const (Y is 1).

當當下的殘餘低頻信號RD處於遞減狀態(數位信號X為0),而前一個時間點輸出偏移頻率與頻率常值f const 的差(Ypre 為1)時,信號選擇單元1333則輸出偏移頻率的負值與頻率常值f const 的和(Y為0)來進行補償。而當當下的殘餘低頻信號RD處於遞增狀態(數位信號X為1),而前一個時間點輸出偏移頻率與頻率常值f const 的和(Ypre 為0)時,信號選擇單元1333持續輸出偏移頻率的負值與頻率常值f const 的和(Y為0)。When the current residual low frequency signal RD is in a decreasing state (digital signal X is 0), and the previous time point output offset frequency The signal selection unit 1333 outputs an offset frequency when the difference from the frequency constant f const (Y pre is 1) The negative value is compensated by the sum of the frequency constants f const (Y is 0). And when the current residual low frequency signal RD is in an increasing state (the digital signal X is 1), and the previous time point output offset frequency When the sum of the frequency constant f const (Y pre is 0), the signal selecting unit 1333 continuously outputs the offset frequency The sum of the negative value and the frequency constant f const (Y is 0).

其中上述的偏移頻率透過前述載波頻率偏移估測暨補償演算法所獲得。而頻率常值f const 則為一定值,預先設定於信號選擇單元1333中。頻率常值f const 的大小取決於前一階段載波頻率偏移估測暨補償演算法的估測誤差(理想上估測誤差小於單位頻率值f U )。例如,設定一頻率差Δf 為透過前述載波頻率偏移估測暨補償演算法獲得的偏移頻率的頻率值與實際的偏移頻率f offset 之間的差。在本實施例中,頻率常值f const 則必須大於上述的頻率差Δf 。如此一來,可透過切換動態估測頻率值f compens (即,)的頻率來調整殘餘頻率偏移(f offset +f compens )的極性,使得動態估測頻率值f compens 的影響力大到足以對基頻信號r [n ]的相位差進行補償。The above offset frequency Obtained by the aforementioned carrier frequency offset estimation and compensation algorithm. The frequency constant value f const is a constant value and is set in advance in the signal selecting unit 1333. The magnitude of the frequency constant f const depends on the estimation error of the previous stage carrier frequency offset estimation and compensation algorithm (ideally the estimated error is less than the unit frequency value f U ). For example, setting a frequency difference Δf is an offset frequency obtained by transmitting the carrier frequency offset estimation and compensation algorithm described above. The difference between the frequency value and the actual offset frequency f offset . In this embodiment, the frequency constant f const must be greater than the frequency difference Δf described above. In this way, the dynamic estimation frequency value f compens can be switched (ie, The frequency of the residual frequency offset ( f offset + f compens ) is adjusted such that the influence of the dynamic estimated frequency value f compens is large enough to compensate for the phase difference of the fundamental frequency signal r [ n ].

另外,在本實施例中,頻率常值f const 亦需符合以下兩個準則,準則一為切換對稱性準則,如下式(11)所示: In addition, in this embodiment, the frequency constant value f const also needs to meet the following two criteria, and the criterion one is a switching symmetry criterion, as shown in the following formula (11):

這樣的準則設定主要是為了避免偏移頻率的負值與頻率常值的和()以及偏移頻率的負值與頻率常值的差()比例懸殊,造成補償基頻信號r[n] 的能力不對稱。Such a criterion setting is mainly to avoid the sum of the negative value of the offset frequency and the frequency constant ( And the difference between the negative value of the offset frequency and the frequency constant ( The ratio is disparity, resulting in an asymmetry in the ability to compensate for the fundamental frequency signal r[n] .

另一則為切換速度準則,如下式(12) The other is the switching speed criterion, as shown in the following equation (12)

其中,M為切換週期,Ts 為信號取樣週期Where M is the switching period and T s is the signal sampling period

由於正弦波或餘弦波皆每四分之一周期改變一次斜率之極性(遞增/遞減狀態),因此每四分之一周期應具有足夠數量的取樣資料,才不會使得信號選擇單元1333來不及動態切換動態估測頻率值f compens 或誤判斜率之極性。但在實際狀況裡,四分之一周期中應具有更多的取樣點,以提供足夠的取樣資料給予高頻拒絕單元進行濾波,降低高頻分量引發載波相位誤修正的機率。Since the sine wave or the cosine wave changes the polarity of the slope (increment/decrement state) every quarter cycle, there should be a sufficient number of samples per quarter cycle so that the signal selection unit 1333 does not make the signal selection unit 1333 less dynamic. Switch the dynamic estimated frequency value f compens or misjudge the polarity of the slope. However, in actual conditions, there should be more sampling points in the quarter cycle to provide sufficient sampling data to the high frequency rejection unit for filtering, reducing the probability of high frequency components causing carrier phase error correction.

載波頻率偏移估測暨補償演算法由處理單元133所包括的一處理器實現,並且此處理器耦接至圖5及圖7中所述信號選擇單元1333以傳送偏移頻率至信號選擇單元1333。所述的處理器可為一固定硬體電路,亦可為一韌體解決方案(即,一般用途處理器配合執行特定的程式碼而實現)。而圖7中用以實現載波相位差修正演算法之硬體電路(即,信號選擇單元1333),亦可由韌體解決方案取代,本發明並不限訂上述的實施方式。The carrier frequency offset estimation and compensation algorithm is implemented by a processor included in the processing unit 133, and the processor is coupled to the signal selection unit 1333 in FIGS. 5 and 7 to transmit an offset frequency. To signal selection unit 1333. The processor may be a fixed hardware circuit or a firmware solution (ie, the general purpose processor cooperates with executing a specific code). The hardware circuit (ie, signal selection unit 1333) for implementing the carrier phase difference correction algorithm in FIG. 7 may also be replaced by a firmware solution, and the present invention is not limited to the above embodiments.

本發明亦提供一種信號接收方法,適用於一信號接收裝置,其中信號接收裝置接收一單載波實數信號,其中單載波實數信號以BPSK調變方式調變而成。The invention also provides a signal receiving method, which is suitable for a signal receiving device, wherein the signal receiving device receives a single carrier real number signal, wherein the single carrier real number signal is modulated by BPSK modulation.

圖8為根據本發明一實施例所繪示信號接收方法的步驟流程圖。請參照圖8,首先在步驟S801時,接收單載波實數信號。然後在步驟S802時,轉換單載波實數信號為一數位實數中頻信號,其中數位實數中頻信號位於一中頻頻率。接著在步驟S803時,根據一同步信號轉換數位實數中頻信號為一基頻信號,其中同步信號位於一本地中頻頻率。再者步驟S804時,執行載波頻率偏移估測暨補償演算法,估測出中頻頻率的一偏移頻率值,並根據偏移頻率值調整本地中頻頻率的頻率值,以補償數位中頻實數信號與基頻信號之間的轉換。其次,在步驟S805時,執行一載波相位差修正演算法,動態調整偏移頻率值,以修正中頻實數信號與同步信號間的一相位差。最後在步驟S806,基頻處理電路解調信號以得到一數位資料。而所述方法的詳細實施方式可以參考上述圖1~圖7所示實施例的說明,在此則不贅述。FIG. 8 is a flow chart showing the steps of a signal receiving method according to an embodiment of the invention. Referring to FIG. 8, first, at step S801, a single carrier real number signal is received. Then, in step S802, the single-carrier real number signal is converted into a digital real IF signal, wherein the digital real IF signal is located at an intermediate frequency. Next, in step S803, the digital real IF signal is converted into a fundamental frequency signal according to a synchronization signal, wherein the synchronization signal is located at a local intermediate frequency. In step S804, the carrier frequency offset estimation and compensation algorithm is performed, an offset frequency value of the intermediate frequency is estimated, and the frequency value of the local intermediate frequency is adjusted according to the offset frequency value to compensate the digital The conversion between the frequency real signal and the fundamental signal. Next, in step S805, a carrier phase difference correction algorithm is executed to dynamically adjust the offset frequency value to correct a phase difference between the intermediate frequency real signal and the synchronization signal. Finally, in step S806, the baseband processing circuit demodulates the signal to obtain a digital data. For the detailed implementation of the method, reference may be made to the description of the embodiment shown in FIG. 1 to FIG. 7 , and details are not described herein.

綜上所述,本發明提供一種信號接收裝置及信號接收方法。此信號接收裝置為一接收BPSK調變而成的單載波信號的接收機,此裝置相對於通用的複數信號接收機而言,具有更低複雜度的特點。然而,載波頻率偏移估測暨補償和載波相位差修正較為困難的問題伴隨而生,為了解決此問題,本發明中提出了一套信號接收方法。在此方法中,藉由過補償程序之輔助,基頻信號的諧波間距得以被拉寬,使得載波頻率偏移估測暨補償演算法能更精準地估測出偏移頻率並補償之,接著載波相位差修正演算法動態調整載波瞬時相位以縮小載波相位差,使得提出的接收裝置 在接收BPSK調變的單載波信號時,受信號上載波頻率偏移和相位差的影響降低。In summary, the present invention provides a signal receiving apparatus and a signal receiving method. The signal receiving device is a receiver that receives a BPSK modulated single carrier signal, and the device has a lower complexity than a general complex signal receiver. However, a problem that carrier frequency offset estimation and compensation and carrier phase difference correction are difficult is accompanied. To solve this problem, a signal receiving method is proposed in the present invention. In this method, the harmonic spacing of the fundamental frequency signal is widened by the aid of the overcompensation procedure, so that the carrier frequency offset estimation and compensation algorithm can more accurately estimate the offset frequency and compensate it. Then the carrier phase difference correction algorithm dynamically adjusts the carrier instantaneous phase to reduce the carrier phase difference, so that the proposed receiving device When receiving a BPSK modulated single carrier signal, it is affected by the carrier frequency offset and phase difference on the signal.

10‧‧‧信號接收裝置10‧‧‧Signal receiving device

110‧‧‧射頻電路110‧‧‧RF circuit

120‧‧‧類比/數位轉換器120‧‧‧ Analog/Digital Converter

130‧‧‧降頻單元130‧‧‧down frequency unit

140‧‧‧基頻處理電路140‧‧‧ fundamental frequency processing circuit

R[n]‧‧‧單載波實數信號R[n]‧‧‧ single carrier real number signal

‧‧‧數位中頻實數信號 ‧‧‧Digital IF real signal

r [n ]‧‧‧基頻信號 r [ n ]‧‧‧ fundamental frequency signal

Claims (16)

一種信號接收裝置,適用於接收一單載波(single carrier)實數信號,其中該單載波實數信號以一二位元相位偏移調變(Binary Phase Shift Keying,BPSK)方式調變而成,包括:一射頻電路,接收該單載波實數信號;一類比/數位轉換器,耦接該射頻電路,接收該單載波實數信號並轉換為一數位中頻實數信號,其中該數位中頻實數信號位於一中頻頻率;一降頻單元,耦接該類比/數位轉換器,根據一同步信號轉換該數位中頻實數信號為一基頻信號,其中該同步信號位於一本地中頻頻率;以及一基頻處理電路,耦接該降頻單元,接收該基頻信號並處理該基頻信號以得到一數位資料,其中,該降頻單元執行一載波頻率偏移估測暨補償演算法,估測該中頻頻率的一偏移頻率值,並根據該偏移頻率值調整該本地中頻頻率的頻率值,以補償該數位中頻實數信號與該基頻信號之間的轉換;以及該降頻單元執行一載波相位差修正演算法,動態調整該偏移頻率值,以修正該中頻實數信號與該同步信號中的一相位差。A signal receiving apparatus is adapted to receive a single carrier real number signal, wherein the single carrier real number signal is modulated by a Binary Phase Shift Keying (BPSK) method, including: An RF circuit receives the single carrier real number signal; a analog/digital converter coupled to the RF circuit receives the single carrier real number signal and converts it into a digital intermediate frequency real number signal, wherein the digital intermediate frequency real number signal is located in one a frequency down frequency unit, coupled to the analog/digital converter, converts the digital intermediate frequency real number signal into a fundamental frequency signal according to a synchronization signal, wherein the synchronization signal is located at a local intermediate frequency; and a fundamental frequency processing a circuit coupled to the down-converting unit, receiving the baseband signal and processing the baseband signal to obtain a digital data, wherein the down-converting unit performs a carrier frequency offset estimation and compensation algorithm to estimate the intermediate frequency An offset frequency value of the frequency, and adjusting a frequency value of the local intermediate frequency according to the offset frequency value to compensate between the digital intermediate frequency real signal and the base frequency signal Converter; and a frequency reduction unit performs carrier phase correction algorithm, the frequency of dynamically adjusting the offset value to correct the real intermediate frequency signal and a phase of the synchronization signal. 如申請專利範圍第1項所述的信號接收裝置,其中該降頻單元包括:一數值控制振盪器,產生該同步信號,其中該同步信號位於 該本地中頻頻率;一數位降頻轉換器(Digital Down Converter,DDC),耦接該類比/數位轉換器以及該數值控制振盪器,根據該同步信號轉換該數位中頻實數信號為該基頻信號;以及一處理單元,耦接該數位降頻轉換器及該數值控制振盪器,傳送一控制信號至該數值控制振盪器,其中該控制信號包括修正後的該中頻頻率值,其中該修正後的該中頻頻率值為預先定義的一本地中頻頻率的頻率值與一動態估測頻率值的和,以及該處理單元動態修正該偏移頻率值而得到該動態估測頻率值,其中,該數位降頻轉換器根據該控制信號中的修正後的中頻頻率值調整該同步信號的該本地中頻頻率,以將數位中頻實數信號轉換為該基頻信號。The signal receiving device of claim 1, wherein the frequency down unit comprises: a numerically controlled oscillator that generates the synchronization signal, wherein the synchronization signal is located a local intermediate frequency, a digital down converter (DDC) coupled to the analog/digital converter and the numerically controlled oscillator, and converting the digital intermediate real signal to the fundamental frequency according to the synchronization signal And a processing unit coupled to the digital down converter and the numerically controlled oscillator to transmit a control signal to the numerically controlled oscillator, wherein the control signal includes the corrected intermediate frequency frequency value, wherein the correction The subsequent intermediate frequency value is a sum of a frequency value of a predefined local intermediate frequency and a dynamically estimated frequency value, and the processing unit dynamically corrects the offset frequency value to obtain the dynamic estimated frequency value, wherein The digital down converter adjusts the local intermediate frequency of the synchronization signal according to the corrected intermediate frequency value in the control signal to convert the digital intermediate frequency real signal into the fundamental signal. 如申請專利範圍第2項所述的接收裝置,其中該載波頻率偏移補償暨估測演算法包括:該處理單元設定一過補償頻率值,其中該過補償頻率值為該預先定義的本地中頻頻率的頻率值與一過補償頻率值的和,並傳送包括該過補償頻率值的該控制信號至該數值控制振盪器;當該數值控制振盪器接收該控制信號時,根據該過補償頻率值產生一過補償同步信號,並傳送該過補償同步信號至該數位降頻轉換器;該數位降頻轉換器接收該過補償同步信號時,該數位降頻轉換器根據該過補償同步信號轉換得到一過補償基頻信號;以及 該處理單元根據該過補償基頻信號得到該偏移頻率值。The receiving device of claim 2, wherein the carrier frequency offset compensation and estimation algorithm comprises: the processing unit setting an overcompensated frequency value, wherein the overcompensated frequency value is in the predefined local a sum of a frequency value of the frequency frequency and an overcompensated frequency value, and transmitting the control signal including the overcompensated frequency value to the numerically controlled oscillator; when the numerically controlled oscillator receives the control signal, according to the overcompensated frequency The value generates an over-compensation synchronization signal, and transmits the over-compensated synchronization signal to the digital down-converter; when the digital-down converter receives the over-compensated synchronization signal, the digital-down converter converts according to the over-compensated synchronization signal Obtaining an over compensated baseband signal; The processing unit obtains the offset frequency value according to the overcompensated baseband signal. 如申請專利範圍第3項所述的信號接收裝置,其中:當該處理單元接收該過補償基頻信號時,該處理單元對該過補償基頻信號取絕對值,並計算取絕對值後的該過補償基頻信號與多個單音信號(single tone)之間的多個相關值(correlation);以及該處理單元判斷該些相關值中最大的相關值為一最大相關值,並求出對應於該最大相關值的該些單音信號的一索引值,並根據該索引值計算得到該偏移頻率值。The signal receiving device of claim 3, wherein: when the processing unit receives the overcompensated baseband signal, the processing unit takes an absolute value of the overcompensated baseband signal and calculates an absolute value. a plurality of correlation values between the overcompensated baseband signal and the plurality of single tone signals; and the processing unit determines that the largest correlation value among the correlation values is a maximum correlation value, and obtains An index value of the tone signals corresponding to the maximum correlation value, and the offset frequency value is calculated according to the index value. 如申請專利範圍第4項所述的信號接收裝置,其中:該過補償基頻信號包括一殘餘低頻信號以及n個諧波信號;該些單音信號分佈於與一估測區間中,彼此間隔一單位頻率值,分別具有一正弦子信號以及一餘弦子信號,其中該n個諧波信號中的一第一諧波信號位於該估測區間中;以及該些單音信號之一與該過補償基頻信號之間該相關值為該些單音信號之一的該正弦子信號與該過補償基頻信號的該第一諧波信號的乘積,並積分後取絕對值與該些單音信號之一的該餘弦子信號與該過補償基頻信號的該第一諧波信號的乘積之積分之絕對值的和。The signal receiving device of claim 4, wherein: the overcompensated baseband signal comprises a residual low frequency signal and n harmonic signals; the monophonic signals are distributed in an estimated interval, spaced apart from each other a unit frequency value having a sinusoidal sub-signal and a cosine sub-signal, wherein a first one of the n harmonic signals is located in the estimated interval; and one of the monophonic signals And the correlation value between the compensated baseband signals is a product of the sinusoidal sub-signal of one of the monophonic signals and the first harmonic signal of the overcompensated baseband signal, and integrated to obtain an absolute value and the tones The sum of the absolute values of the integral of the product of the cosine sub-signal of one of the signals and the first harmonic signal of the overcompensated baseband signal. 如申請專利範圍第2項所述的信號接收裝置,其中該處理單元包括:一高頻拒絕單元; 一微分器,耦接該高頻拒絕單元;一信號選擇單元,耦接該微分器;以及該載波相位差修正演算法包括:該高頻拒絕單元接收該基頻信號並濾除該基頻信號中的一高頻成份得到一殘餘低頻信號;該微分器從該高頻拒絕單元接收該殘餘低頻信號,並微分該殘餘低頻信號而得到一指示信號;以及該信號選擇單元接收該指示信號,並根據該指示信號調整該偏移頻率值而得到該動態估測頻率值。The signal receiving device of claim 2, wherein the processing unit comprises: a high frequency rejecting unit; a differentiator coupled to the high frequency rejecting unit; a signal selecting unit coupled to the differentiator; and the carrier phase difference correction algorithm comprising: the high frequency rejecting unit receiving the baseband signal and filtering the baseband signal a high frequency component obtains a residual low frequency signal; the differentiator receives the residual low frequency signal from the high frequency rejecting unit, and differentiates the residual low frequency signal to obtain an indication signal; and the signal selecting unit receives the indication signal, and The offset frequency value is adjusted according to the indication signal to obtain the dynamic estimated frequency value. 如申請專利範圍第6項所述的信號接收裝置,其中該高頻拒絕單元包括:一絕對值計算器,接收該基頻信號,計算得到該基頻信號的絕對值;一低通濾波器,耦接該絕對值計算器,接收該基頻信號的絕對值,濾除該基頻信號的絕對值的該高頻成份;一降取樣單元,耦接該低通濾波器,接收該基頻信號的絕對值,並降取樣該基頻信號的絕對值得到該殘餘低頻信號。The signal receiving device of claim 6, wherein the high frequency rejecting unit comprises: an absolute value calculator, receiving the fundamental frequency signal, and calculating an absolute value of the fundamental frequency signal; a low pass filter, The absolute value calculator is coupled to receive the absolute value of the baseband signal, and filter the high frequency component of the absolute value of the baseband signal; a downsampling unit coupled to the low pass filter to receive the baseband signal The absolute value of the fundamental frequency signal is downsampled to obtain the residual low frequency signal. 如申請專利範圍第6項所述的信號接收裝置,其中該信號選擇單元包括:一中繼單元,接收該指示信號,並轉換該指示信號為一數位信號;一否互斥或閘(NXOR gate),具有第一輸入端、第二輸入端 以及輸出端,其中該否互斥或閘的第一輸入端耦接該中繼單元並接收該數位信號,該否互斥或閘的輸出端輸出一選擇信號;一延遲單元,耦接於該否互斥或閘的第二輸入端與輸出端之間,延遲該選擇信號為一延遲選擇信號,並傳送該延遲選擇信號至該否互斥或閘的第二輸入端;一選擇器,根據該選擇信號以輸出該動態估測頻率值,其中該選擇器根據選擇信號選擇該偏移頻率值的負值與一頻率常值的和或該偏移頻率值的負值與該頻率常值的差輸出為該動態估測頻率值。The signal receiving device of claim 6, wherein the signal selecting unit comprises: a relay unit, receiving the indication signal, and converting the indication signal into a digital signal; and a mutual exclusion or gate (NXOR gate) ) having a first input and a second input And an output end, wherein the first input end of the mutex or the gate is coupled to the relay unit and receives the digital signal, and the output of the mutex or the gate outputs a selection signal; a delay unit coupled to the Between the second input end and the output end of the mutex or the gate, delaying the selection signal as a delay selection signal, and transmitting the delay selection signal to the second input terminal of the non-mutation or gate; a selector, according to Selecting a signal to output the dynamic estimated frequency value, wherein the selector selects a sum of a negative value of the offset frequency value and a frequency constant value or a negative value of the offset frequency value and the frequency constant value according to the selection signal The difference output is the dynamic estimated frequency value. 一個信號接收方法,適用於一信號接收裝置,其中該信號接收裝置接收一單載波實數信號,其中該單載波實數信號以一二位元相位偏移調變方式調變而成,所述信號接收方法包括:接收該單載波實數信號;轉換該單載波實數信號為一數位中頻實數信號,其中該數位中頻實數信號位於一中頻頻率;根據一同步信號轉換該數位中頻實數信號為一基頻信號,其中該同步信號位於一本地中頻頻率;執行一載波頻率頻率偏移估測暨補償演算法,估測該中頻頻率的一偏移頻率值,並根據該偏移頻率值調整該本地中頻頻率的頻率值,以補償該數位中頻實數信號與該基頻信號之間的轉換;執行一載波相位差修正演算法,動態調整該偏移頻率值,以修正該中頻實數信號與該同步信號間的一相位差;以及 處理該基頻信號以得到一數位資料。A signal receiving method is applicable to a signal receiving apparatus, wherein the signal receiving apparatus receives a single carrier real number signal, wherein the single carrier real number signal is modulated by a two-bit phase offset modulation method, and the signal receiving is performed. The method includes: receiving the single carrier real number signal; converting the single carrier real number signal into a digital intermediate frequency real number signal, wherein the digital intermediate frequency real number signal is located at an intermediate frequency; and converting the digital intermediate frequency real number signal according to a synchronization signal a baseband signal, wherein the synchronization signal is located at a local intermediate frequency; performing a carrier frequency frequency offset estimation and compensation algorithm, estimating an offset frequency value of the intermediate frequency, and adjusting according to the offset frequency value a frequency value of the local intermediate frequency to compensate for conversion between the digital intermediate frequency real signal and the base frequency signal; performing a carrier phase difference correction algorithm to dynamically adjust the offset frequency value to correct the intermediate frequency real number a phase difference between the signal and the synchronization signal; The baseband signal is processed to obtain a digital data. 如申請專利範圍第9項所述的信號接收方法,其中根據該同步信號轉換該數位中頻實數信號為該基頻信號的步驟包括:動態修正該偏移頻率值而得到該動態估測頻率值;產生一控制信號,其中該控制信號包括修正後的該中頻頻率值,其中該修正後的該中頻頻率值為預先定義的一本地中頻頻率的頻率值與該動態估測頻率值的和;根據該控制信號產生該同步信號;調整該本地中頻頻率的頻率值為該修正後的中頻頻率值;以及根據該同步信號轉換該數位中頻實數信號為該基頻信號。The signal receiving method according to claim 9, wherein the step of converting the digital intermediate frequency real signal into the fundamental frequency signal according to the synchronization signal comprises: dynamically correcting the offset frequency value to obtain the dynamic estimated frequency value. Generating a control signal, wherein the control signal includes the corrected intermediate frequency frequency value, wherein the corrected intermediate frequency frequency value is a predetermined frequency value of a local intermediate frequency and the dynamic estimated frequency value And generating a synchronization signal according to the control signal; adjusting a frequency value of the local intermediate frequency to the corrected intermediate frequency frequency value; and converting the digital intermediate frequency real signal to the fundamental frequency signal according to the synchronization signal. 如申請專利範圍第10項所述的信號接收方法,其中該該載波頻率偏移補償暨估測演算法包括:設定一過補償頻率值為為該預先定義的本地中頻頻率的頻率值與一過補償頻率值的和;根據該過補償頻率值產生一過補償同步信號;根據該過補償同步信號中的該過補償頻率值產生一過補償基頻信號;以及根據該過補償基頻信號得到該偏移頻率值。The signal receiving method according to claim 10, wherein the carrier frequency offset compensation and estimation algorithm comprises: setting an overcompensation frequency value to a frequency value of the predefined local intermediate frequency and a And overcompensating the sum of the frequency values; generating an overcompensated synchronization signal according to the overcompensated frequency value; generating an overcompensated baseband signal according to the overcompensated frequency value in the overcompensated synchronizing signal; and obtaining the overcompensated baseband signal according to the overcompensated baseband signal The offset frequency value. 如申請專利範圍第11項所述的信號接收方法,其中根據該過補償基頻信號得到該偏移頻率值的步驟包括:對該過補償基頻信號取絕對值,並計算取絕對值後的該過補 償基頻信號與多個單音信號(single tone)之間的多個相關值(correlation);以及判斷該些相關值中最大的相關值為一最大相關值,並求出對應於該最大相關值的該些單音信號的一索引值,並根據該索引值對應該估測頻率值。The signal receiving method according to claim 11, wherein the step of obtaining the offset frequency value according to the overcompensated baseband signal comprises: taking an absolute value of the overcompensated baseband signal, and calculating an absolute value Overcompensation Compensating for a plurality of correlations between the baseband signal and the plurality of single tone signals; and determining that the largest correlation value among the correlation values is a maximum correlation value, and finding the maximum correlation An index value of the monophonic signals of the value, and the frequency value is estimated according to the index value. 如申請專利範圍第12項所述的信號接收方法,其中:該過補償基頻信號包括一殘餘低頻信號以及n個諧波信號;該些單音信號分佈於與一估測區間中,彼此間隔一單位頻率值,分別具有一正弦子信號以及一餘弦子信號,其中該n個諧波信號中的一第一諧波信號位於該估測區間中;以及該些單音信號之一與該過補償基頻信號之間該相關值為該些單音信號之一的該正弦子信號與該過補償基頻信號的絕對值之乘積積分後取絕對值與該些單音信號之一的該餘弦子信號與該過補償基頻信號的絕對值之乘積積分後絕對值的和。The signal receiving method of claim 12, wherein the overcompensated baseband signal comprises a residual low frequency signal and n harmonic signals; the monophonic signals are distributed in an estimated interval and spaced apart from each other a unit frequency value having a sinusoidal sub-signal and a cosine sub-signal, wherein a first one of the n harmonic signals is located in the estimated interval; and one of the monophonic signals And the correlation value between the compensated fundamental frequency signals is a product of the sinusoidal sub-signal of one of the monophonic signals and the absolute value of the overcompensated baseband signal, and the absolute value and the cosine of one of the monophonic signals are taken The sum of the absolute values of the product of the sub-signal and the absolute value of the over-compensated baseband signal. 如申請專利範圍第11項所述的信號接收方法,其中該載波相位差修正演算法包括:濾除該基頻信號中的一高頻成份得到一殘餘低頻信號;微分該殘餘低頻信號而得到一指示信號;以及根據該指示信號調整該偏移頻率值而得到該動態估測頻率值。The signal receiving method according to claim 11, wherein the carrier phase difference correction algorithm comprises: filtering a high frequency component of the baseband signal to obtain a residual low frequency signal; and differentiating the residual low frequency signal to obtain a And indicating the signal; and adjusting the offset frequency value according to the indication signal to obtain the dynamic estimated frequency value. 如申請專利範圍第14項所述的信號接收方法,其中濾除該基頻信號中的該高頻成份得到該殘餘低頻信號的步驟包括: 計算得到該基頻信號的絕對值;濾除該基頻信號的絕對值的該高頻成份;以及降取樣該基頻信號的絕對值得到該殘餘低頻信號。The signal receiving method of claim 14, wherein the step of filtering the high frequency component in the baseband signal to obtain the residual low frequency signal comprises: Calculating an absolute value of the baseband signal; filtering the high frequency component of the absolute value of the baseband signal; and downsampling the absolute value of the baseband signal to obtain the residual low frequency signal. 如申請專利範圍第14項所述的信號接收方法,其中根據該指示信號調整該估測頻率值為該動態估測頻率值的步驟包括:轉換該指示信號為一數位信號;根據該數位信號,以及一延遲選擇信號,輸出一選擇信號;以及根據該選擇信號輸出該動態估測頻率值,其中該動態估測頻率值為該偏移頻率值的負值與一頻率常值的和,或該偏移頻率值的負值與該頻率常值的差。The signal receiving method of claim 14, wherein the step of adjusting the estimated frequency value according to the indication signal to the dynamic estimated frequency value comprises: converting the indication signal to a digital signal; according to the digital signal, And a delay selection signal, outputting a selection signal; and outputting the dynamic estimation frequency value according to the selection signal, wherein the dynamic estimation frequency value is a sum of a negative value of the offset frequency value and a frequency constant value, or The difference between the negative value of the offset frequency value and the constant value of the frequency.
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Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5260707A (en) * 1988-12-22 1993-11-09 Hughes Aircraft Company Phase coherent interference signal suppression system and method

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5260707A (en) * 1988-12-22 1993-11-09 Hughes Aircraft Company Phase coherent interference signal suppression system and method

Non-Patent Citations (7)

* Cited by examiner, † Cited by third party
Title
Chih-Cheng Fu; To-Ping Wang; Kang-Chuan Chang,; Chung-Hao Liao; Tzi-Dar Chiueh, "A Real-Time Digital Baseband Channel Emulation System for OFDM Communications," in Circuits and Systems, 2006. APCCAS 2006. IEEE Asia Pacific Conference on , vol., no., pp.984-987, 4-7 Dec. 2006 *
Chuang, K.; Yeh, D.; Barale, F.; Perumana, B.; Sarkar, S.; Sen, P.; Pinel, S.; Laskar, J., "A 17pJ/bit broadband mixed-signal demodulator in 90nm CMOS," in Microwave Symposium Digest (MTT), 2010 IEEE MTT-S International , vol., no., pp.904-907, 23-28 May 2010 *
Jheng-Ru Liang; Chih-Hung Kuo, "LS-based joint estimation of carrier frequency offset and IQ imbalance in OFDM systems," in Next-Generation Electronics (ISNE), 2010 International Symposium on , vol., no., pp.52-55, 18-19 Nov. 2010 *
Jian Luo; Kortke, A.; Keusgen, W., "Semi-Blind Iterative Joint Estimation of Frequency Selective I/Q-Imbalance and Modulator Offset Error in Direct-Conversion Transmitters," in Vehicular Technology Conference Fall (VTC 2010-Fall), 2010 IEEE 72nd , vol., no., pp.1-5, 6-9 Sept. 2010 *
Jonghun Park; Yusung Lee; Hyuncheol Park, "Joint Estimation of Carrier Frequency Offset and I/Q Imbalance for Direct Conversion OFDM System with Constrained Preambles," in Signals, Systems and Computers, 2007. ACSSC 2007. Conference Record of the Forty-First Asilomar Conference on , vol., no., pp.1786-1790, 4-7 Nov. 2007 *
Lanante, L.A.; Imashioya, R.; Kurosaki, M.; Ochi, H., "A low complexity joint parameter estimation scheme for Carrier Frequency Offset and I/Q Imbalance," in Advanced Communication Technology, 2009. ICACT 2009. 11th International Conference on , vol.02, no., pp.1365-1369, 15-18 Feb. 2009 *
Yuce, M.R.; Wentai Liu, "A low-power multirate differential PSK receiver for space applications," in Vehicular Technology, IEEE Transactions on , vol.54, no.6, pp.2074-2084, Nov. 2005 *

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