JP5094524B2 - High frequency coupled line and high frequency filter - Google Patents

Description

  The present invention relates to a high-frequency coupling line, and more particularly, to a high-frequency coupling line used in a microwave band and a millimeter wave band, and a high-frequency filter using these high-frequency coupling lines.

  A coupling line in which two distributed constant lines are arranged close to each other in parallel and electromagnetically coupled has been widely used as a component of a filter or a directional coupler (see, for example, Patent Document 1).

  As one of the representative ones, for example, there is a so-called interdigital coupling line as a two-terminal circuit configured by arranging two distributed constant lines with open ends arranged in parallel in opposite directions. FIG. 13 shows an interdigital coupling line constituted by a microstrip line. In FIG. 13, 1 is a dielectric substrate, 2 is a ground conductor, 3a and 3b are input / output strip conductors, 4a and 4b are coupled line strip conductors connected to the input / output strip conductors 3a and 3b, and 5 is a coupled line strip conductor. 4a and 4b are the conductor gaps, 7a and 7b are the open ends of the ends of the coupled line strip conductors 4a and 4b, and 10 is the electromagnetic coupling between the coupled line strip conductors 4a and 4b arranged in parallel. It is a set of two-terminal circuit coupling line sections. The interdigital coupling line having such a configuration is the strongest coupling at the frequency at which the electric length of two distributed constant line portions that are electromagnetically coupled in parallel is 90 degrees, and at an odd multiple of the frequency, On the other hand, it has a frequency characteristic with periodicity as shown in FIG. In FIG. 14, the frequency at which the electrical length of the two coupled line strip conductors 4a and 4b to be electromagnetically coupled is 90 degrees is defined as f0. This type of coupled line is often designed and used at a frequency where the electrical length is 90 degrees or less than 90 degrees from the viewpoint of miniaturization.

JP 2004-104588 A

  However, in the interdigital type coupled line having an electrical length of 90 degrees at the design frequency of the circuit including the coupled line, a frequency band such as three times the above design frequency due to the relationship of the periodic frequency characteristics as described above. Thus, the coupling becomes strong as with the design frequency. For this reason, for example, in a band pass filter, when the design frequency is the center frequency of the pass band, the signal is easily transmitted in a frequency band near three times the center frequency. In addition, if the electrical length of the coupled line is selected to be about 45 degrees shorter than 90 degrees due to a demand for circuit miniaturization or physical restrictions, the electrical length of the coupled line becomes 90 degrees at twice the frequency. Therefore, in this case, the signal transmission amount tends to increase near twice the design frequency. In addition to the ease of periodic signal transmission in the coupled line portion, there is a problem that the attenuation amount of the filter is significantly deteriorated when the higher-order resonance of the resonator used in the filter is superimposed.

The present invention has been made to solve such a problem, and an object of the present invention is to obtain a high-frequency coupled line that exhibits required coupling only in the vicinity of a predetermined frequency band and has few unnecessary couplings in other frequency bands. And
It is another object of the present invention to obtain a high frequency filter with a low spurious response using such a coupled line.

The present invention is a set of two-terminal circuits in which two distributed constant lines having one end as a short-circuited end or an open end and an input / output terminal at the other end are arranged in parallel and are electromagnetically coupled to each other. A coupled line portion; and one or more stub-shaped distributed constant lines having one end as a short-circuited end or an open end, and the stub-shaped distributed constant line corresponds to the distributed constant line constituting the two-terminal circuit coupled line portion. Te, substantially parallel, and closely spaced, the other end of the stub-like distributed constant line, the other end of the entering output terminal side of the distributed constant line constituting said two-terminal circuit coupling line section is a high-frequency coupling line, characterized in that connected to the vicinity minute.

The present invention is a set of two-terminal circuits in which two distributed constant lines having one end as a short-circuited end or an open end and an input / output terminal at the other end are arranged in parallel and are electromagnetically coupled to each other. A coupled line portion; and one or more stub-shaped distributed constant lines having one end as a short-circuited end or an open end, and the stub-shaped distributed constant line corresponds to the distributed constant line constituting the two-terminal circuit coupled line portion. Te, substantially parallel, and closely spaced, the other end of the stub-like distributed constant line, the other end of the entering output terminal side of the distributed constant line constituting said two-terminal circuit coupling line section since a high frequency coupling line, characterized in that connected to the vicinity minutes, only exhibits the required binding around a predetermined frequency band, it is possible to reduce the unnecessary coupling at other frequency bands.

Embodiment 1 FIG.
FIG. 1 is a perspective view showing a configuration of a high-frequency coupling line according to Embodiment 1 of the present invention. In FIG. 1, a microstrip line type coupled line is shown as an example of the high frequency coupled line according to the first embodiment. FIG. 2 is an equivalent circuit of the high-frequency coupling line in FIG. In these drawings, reference numeral 1 denotes a dielectric substrate (dielectric layer) made of, for example, a ceramic material, and 2 denotes a ground conductor attached to the lower surface of the dielectric substrate 1. Reference numerals 3a and 3b denote a pair of input / output strip conductors (input / output terminals) each having a substantially rectangular shape provided on the upper surface of the dielectric substrate 1 so that one side is aligned with one of the left and right sides of the dielectric substrate 1. ). Reference numerals 4a and 4b denote elongated and substantially rectangular coupled line strip conductors (distributed constant lines) which are arranged close to each other in parallel on the upper surface of the dielectric substrate 1 and connected to the input / output strip conductors 3a and 3b, respectively. Reference numeral 5 denotes a conductor gap between the two coupled line strip conductors 4a and 4b. 6a and 6b are stub-like strip conductors (stub-like distributed constant lines) which are respectively attached to the coupled line strip conductors 4a and 4b and are provided in a direction perpendicular to the longitudinal direction of the coupled line strip conductors 4a and 4b. is there. Reference numerals 7a and 7b denote open ends at the front ends of the coupled line strip conductors 4a and 4b, respectively. Reference numerals 8a and 8b denote open ends at the front ends of the stub-like strip conductors 6a and 6b, respectively. Reference numerals 9a and 9b denote connecting portions of the stub strip conductors 6a and 6b to the coupled line strip conductors 4a and 4b. Reference numeral 10 denotes a set of two-terminal circuit coupling line portions formed by arranging the coupling line strip conductors 4a and 4b substantially in parallel and mutually electromagnetically coupling them. The electrical length θ shown in FIG. 2 is all 30 degrees at the design frequency f0. Therefore, the total electrical length of the coupled line strip conductors 4a and 4b is approximately 90 degrees at the design frequency f0, and the electrical length of the stub-shaped strip conductors 6a and 6b. The length is approximately 30 degrees.

  The coupled line strip conductors 4a and 4b are arranged in opposite directions to each other and are arranged close to each other in parallel. The coupled line strip conductors 4a and 4b are provided at substantially central portions of the upper surface of the dielectric substrate 1 so as to be substantially parallel to the upper and lower sides (two sides in the longitudinal direction) of the upper surface of the dielectric substrate 1, respectively. It has been. The coupled line strip conductors 4a and 4b are respectively extended from the input / output strip conductors 3a and 3b as starting points, and the positions of the open ends 7a and 7b at the distal ends thereof are the other coupled line strips in the longitudinal direction. Up to the position of the starting point of the conductors 4b and 4a. Therefore, as shown in FIG. 1, in the longitudinal direction of the dielectric substrate 1, there is no portion where the coupled line strip conductors 4a and 4b and the input / output strip conductors 3a and 3b are provided side by side. Further, as shown in FIG. 1, the connection portions 9a and 9b of the stub-shaped strip conductors 6a and 6b to the coupled line strip conductors 4a and 4b are provided in the middle of the coupled line strip conductors 4a and 4b (in the example of FIG. It is provided in the vicinity of the central portion in the direction, at a position slightly close to the open ends 7a and 7b).

  In the present embodiment, all that is required is that the coupled line strip conductors 4a and 4b have an electrical length of approximately 90 degrees at the design frequency f0, and the stub-shaped strip conductors 6a and 6b have approximately 30 degrees at the design frequency f0. The connecting portions 9a and 9b of the stub-shaped strip conductors 6a and 6b to the coupled line strip conductors 4a and 4b are designed from the open ends 7a and 7b of the coupled line strip conductors 4a and 4b. It is arranged so that the electrical length is approximately 30 degrees at f0.

  Thus, the high-frequency coupling line according to the present embodiment is a coupling that is two distributed constant lines having one end as a short-circuited end or an open end and the other end including input / output strip conductors 3a and 3b as input / output terminals. A set of two-terminal circuit coupling line portions 10 formed by arranging line strip conductors 4a and 4b substantially in parallel and mutually electromagnetically coupled, and one or a plurality of stubs whose one end is a short-circuited end or an open end The stub-shaped strip conductors 6a and 6b, which are linear distributed constant lines, are configured such that the other ends of the stub-shaped strip conductors 6a and 6b are connected in the middle of the coupled line strip conductors 4a and 4b.

Next, the operation will be described.
FIG. 3 shows an equivalent circuit of the high-frequency coupling line according to the present embodiment at a frequency three times the design frequency f0. At a frequency three times f0, all the electrical lengths θ in this figure are 90 degrees. The stub-shaped strip conductors 6a and 6b short-circuit the coupled line strip conductors 4a and 4b to the ground conductor 2 at the connection portions 9a and 9b to the coupled line strip conductors 4a and 4b in order to cause the shunt series resonance. Therefore, an equivalent circuit as shown in FIG. When the three coupled line portions in FIG. 3A are individually rewritten with a two-terminal circuit, FIG. 3B is obtained. The coupled line in the center is a combination of two short-circuited short-circuited lines arranged in opposite directions. Such a coupled line has a distributed constant of 270 degrees (−90 degrees) when the electrical length is 90 degrees. It is known to behave equivalent to a track. For this reason, a circuit like FIG.3 (c) is obtained. Therefore, it can be seen that the high-frequency coupled line of the present embodiment is equivalent to a two-stage band-stop filter using two quarter-wave resonators at a frequency three times the design frequency. For this reason, signal transmission is suppressed in the vicinity of three times the frequency, and the high-frequency coupling line of the present embodiment exhibits frequency characteristics as shown in FIG.

  As described above, in the high-frequency coupled line of the first embodiment, the stub-shaped strip conductors 6a and 6b attached to the coupled line strip conductors 4a and 4b, their electrical lengths, their attachment positions, and the like are appropriately selected. Unlike a normal interdigital coupled line having an electrical length of 90 degrees at the design frequency, the passage loss becomes large in the vicinity of a frequency three times the design frequency. For this reason, there is an effect that transmission of unnecessary signals at frequencies other than the design frequency is small. As a result, it is possible to obtain a high-frequency coupling line that exhibits a required coupling only in the vicinity of a predetermined frequency band and has few unnecessary couplings in other frequency bands. Further, by appropriately selecting the width of the coupled line strip conductors 4a and 4b, the size of the conductor gap 5, the width of the stub strip conductors 6a and 6b, etc., the high frequency coupled line according to the present embodiment operates as a bandpass filter. In this case, it is possible to obtain a filter with less unnecessary spurious response on the high band side of the pass band as compared with the case where a conventional coupled line is used.

Embodiment 2. FIG.
FIG. 5 is a perspective view showing the configuration of the high-frequency coupling line according to Embodiment 2 of the present invention. In FIG. 5, a microstrip line type coupled line is shown as an example as the high frequency coupled line according to the second embodiment. FIG. 6 is an equivalent circuit of the coupled line of FIG. In these drawings, reference numerals 1 to 9 are the same as those in the first embodiment. Further, the electrical length θ shown in FIG. 6 is the same as that of the high frequency coupling line of the first embodiment in that all the electrical lengths θ are 30 degrees at the design frequency f0. However, in the high-frequency coupling line of the present embodiment, as shown in FIG. 5, the stub-shaped strip conductors 6a and 6b are arranged in close proximity to the coupled-line strip conductors 4a and 4b, respectively, so as to be stub-shaped. The difference is that the strip conductors 6a and 6b and the stub-like strip conductors 6a and 6b are electromagnetically coupled. In the example of FIG. 5, only a part of the coupling line strip conductors 4a and 4b in the vicinity of the ends (that is, a predetermined length in the vicinity of the open ends 7a and 7b) is divided into two forks, and one of them is a stub-shaped strip conductor. 6a and 6b are configured, and the other is the tip of the coupled line strip conductors 4a and 4b. In the example of FIG. 5, the widths of the end portions of the coupled line strip conductors 4a and 4b are slightly larger than the widths of the stub-like strip conductors 6a and 6b. In the second embodiment, the coupled line strip conductors 4a and 4b have an electrical length of approximately 90 degrees at the design frequency, and the stub-shaped strip conductors 6a and 6b have an electrical length of approximately 30 degrees at the design frequency. And the connecting portions 9a, 9b of the stub-shaped strip conductors 6a, 6b to the coupled line strip conductors 4a, 4b are arranged in the middle of the coupled line strip conductors 4a, 4b. . Since other configurations are the same as those of the first embodiment, the description thereof is omitted here.

  The operation of the high-frequency coupling line of the second embodiment is basically the same as that of the high-frequency coupling line of the first embodiment. In the second embodiment, the stub-shaped strip conductors 6a and 6b are connected to the coupling line. The strip conductors 4a and 4b are electromagnetically coupled. For this reason, the external Q when the stub is regarded as a series resonant circuit of a shunt has a feature that it is larger than that when the stub is not electromagnetically coupled. The stub-shaped strip conductors 6a and 6b reduce signal transmission in a band three times the design frequency, but also affect the characteristics as a coupled line at the design frequency. For this reason, it is desirable that the width of the stub-shaped strip conductors 6a and 6b is minimized, but the width of the stub-shaped strip conductors 6a and 6b that can be realized is limited due to the manufacturing rules of the dielectric substrate. . Since the stub-shaped strip conductors 6a and 6b of the coupled line according to the second embodiment have an external Q value that is increased by electromagnetic coupling with the coupled line strip conductor as described above, the coupled line strip conductor 4a. , 4b behave equivalently to the stub-like strip conductors 4a, 4b which are not electromagnetically coupled and have a small width. Therefore, in addition to the effects of the high-frequency coupling line of the first embodiment, the high-frequency coupling line of the second embodiment has little deterioration in characteristics at the design frequency f0 of the coupling line, and does not require a conductor pattern with a small width. It has the effect that it is easy to manufacture in the point. Furthermore, since the stub-shaped strip conductor 6 is arranged along the coupled line strip conductor 4, the circuit width as the coupled line is small and the effect of being small is also exhibited.

Embodiment 3 FIG.
FIG. 7 is a perspective view showing the configuration of the high-frequency coupling line according to Embodiment 3 of the present invention. In FIG. 7, a microstrip line type coupled line is shown as an example of the high frequency coupled line according to the third embodiment. FIG. 8 is an equivalent circuit of the coupled line of FIG. In these drawings, reference numerals 1 to 9 are the same as those in the first and second embodiments. The electrical length θ shown in FIG. 8 (a) is 45 degrees at the design frequency f0, and FIGS. 8 (b) and 8 (c) correspond to circuits at twice the design frequency. The electrical length θ is all 90 degrees. It is. In the high-frequency coupling line according to the third embodiment, the stub-like strip conductors 6a and 6b are arranged in parallel and close to the coupling line strip conductors 4a and 4b as in the second embodiment. However, the point that the stub-like strip conductors 6a and 6b have the same length as the coupled line strip conductors 4a and 4b in the longitudinal direction is different from the second embodiment.

  In the high frequency coupling line of the third embodiment, the electrical length at the design frequency of the coupling line strip conductors 4a and 4b and the stub-like strip conductors 6a and 6b is 45 degrees, which is shorter than 90 degrees. The transmission level increases at a frequency twice as high as the design frequency and an odd number multiple of the double frequency. Also in the third embodiment, since the stub-shaped strip conductors 6a and 6b are electromagnetically coupled to the coupled line strip conductors 4a and 4b, the stub-shaped strip conductors 6a and 6b are regarded as shunt series resonance circuits. The external Q value of the stub is larger than that of the stub-like strip conductor having the same width and not electromagnetically coupled. Therefore, the stub strip conductors 4a and 4b electromagnetically coupled to the coupled line strip conductors 4a and 4b are equivalent to the stub strip conductors 6a and 6b having a small width not electromagnetically coupled to the coupled line strip conductors 4a and 4b. It can be considered. Therefore, the circuit of FIG. 8A can be expressed as shown in FIG. 8B in a band twice the design frequency. When the electrical length is an odd multiple of 90 degrees, the coupling line in the center of the figure is equivalent to a distributed constant line having an electrical length of an odd multiple of 90 degrees. Therefore, the circuit of FIG. ). The circuit of FIG. 8C is a circuit of a two-stage band rejection filter. From this, it can be seen that the high-frequency coupling line of the present embodiment has a large passing loss at an odd number of times twice the frequency. . Thus, the high frequency coupling line of the present embodiment exhibits frequency characteristics as shown in FIG.

  The effect obtained by the high frequency coupled line of the third embodiment is basically the same as that of the second embodiment, but the electrical length of the coupled line strip conductors 4a and 4b at the design frequency is less than 90 degrees. In this case, as in the present embodiment, the stub-like strip conductors 6a and 6b are electromagnetically coupled to have substantially the same length as the coupled line strip conductors 4a and 4b, so that unnecessary in a frequency range higher than the design frequency is unnecessary. Signal equivalence can be effectively suppressed. Further, since the external Q value of the stub-like strip conductors 6a and 6b can be increased by electromagnetic field coupling, the adverse effect on the coupling characteristics due to the addition of the stub-like strip conductors 6a and 6b at the design frequency can be minimized. effective.

Embodiment 4 FIG.
FIG. 10 is a perspective view showing the configuration of the high-frequency filter according to Embodiment 4 of the present invention. FIG. 10 shows a microstrip line type band-pass filter as an example of the high-frequency filter according to the fourth embodiment. FIG. 11 is an equivalent circuit of the high frequency filter of FIG. Reference numerals 1 to 7 shown in these drawings are the same as those in the first embodiment. The electrical length θ1 shown in FIG. 11A is 90 degrees at the design frequency f0, and θ2 is 30 degrees at the design frequency f0.

  In the high frequency filter of the fourth embodiment, as shown in FIG. 10, the stub-shaped strip conductors 6-1a and 6-3b are connected to the coupling line strip conductor 4-1a and the input / output strip conductor 3a, respectively. The coupling line strip conductor 4-3b and the input / output strip conductor 3b are attached to the connection position, and are electromagnetically coupled to the coupling line strip conductors 4-1a and 4-3b substantially parallel to each other. The first high-frequency coupling line is formed with the electrical length of 30 degrees at the design frequency f0 so that the stub-like strip conductors 6-1a and 6-3b become 90 degrees in the triple band.

  As shown in FIG. 10, one end of the coupled line strip conductor 4-1a is connected to the input / output strip conductor 3a, and the tip of the other end is an open end or a short-circuit end 7-1a. Similarly, one end of the coupled line strip conductor 4-3b is connected to the input / output strip conductor 3b, and the tip of the other end is an open end or a short-circuit end 7-3b.

  Further, a second composed of coupled line strip conductors 4-2a and 4-1b between two coupled line strip conductors 4-1a and 4-3b constituting the first high-frequency coupled line. A high-frequency coupled line and a third high-frequency coupled line composed of coupled line strip conductors 4-2b and 4-3a are interposed. As shown in FIG. 10, the second high-frequency coupled line has stub-like strip conductors 6-2a and 6-1b substantially parallel and adjacent to the coupled line strip conductors 4-2a and 4-1b, respectively. They are arranged and electromagnetically coupled to each other. Similarly, in the third high-frequency coupling line, the stub-shaped strip conductors 6-3a and 6-2b are disposed substantially parallel to and in the vicinity of the coupling line strip conductors 4-3a and 4-2b, respectively. It is configured by electromagnetic coupling. Also, one ends of the coupled line strip conductors 4-2a and 4-1b are connected to each other, and the other ends are open ends or short-circuit ends 7-2a and 7-1b. Similarly, one ends of the coupled line strip conductors 4-3a and 4-2b are connected to each other, and the other ends are open ends or short-circuit ends 7-3a and 7-2b.

  Also, as shown in FIG. 10, a conductor gap 5-1 is provided between the coupled line strip conductors 4-1a and 4-1b, and these are electromagnetically coupled to each other. Further, a conductor gap 5-2 is provided between the coupled line strip conductors 4-2a and 4-2b, and these are also electromagnetically coupled to each other. Similarly, the coupled line strip conductors 4-3a and 4- A conductor gap 5-3 is provided between 3b, and these are also electromagnetically coupled to each other.

  Thus, the high frequency filter of the fourth embodiment is a filter formed by cascading the first to third high frequency coupling lines. Although not clearly shown in FIGS. 10 and 11, the resonance frequency f0 may be adjusted by interposing a short distributed constant line between adjacent high-frequency coupling lines.

  Also in the present embodiment, in the first high-frequency coupled line, the two coupled line strip conductors 4 have one end 7 as a short-circuited end or an open end, and the other end is an input / output strip conductor 3a that is an input / output terminal. , 3b, and the coupled line strip conductors 4 are arranged substantially in parallel, and one end of the stub-shaped strip conductor 6 is a short-circuited end or an open end, and the other end is the input / output of the coupled line strip conductor 4 It is connected to the portion near the other end on the strip conductor 3 side (or the middle portion between one end which is the short-circuited or open end of the coupling line strip conductor 4 and the other end on the input / output strip conductor 3 side). .

  However, in the fourth embodiment, as shown in FIG. 10, the stub-shaped strip conductors 6-1a and 6-3b are connected to the vicinity of the input / output strip conductor 3 side end. Unlike the stub-like strip conductors 6-1a and 6-3b, the lengths of the coupled line strip conductors 4-1a and 4-3b are different. Similarly, the lengths of the stub-shaped strip conductors 6-2a and 6-1b and the coupled line strip conductors 4-2a and 4-1b are different, and the stub-shaped strip conductors 6-3a and 6-2b are coupled to the coupled line strip. The lengths of the conductors 4-3a and 4-2b are different. However, the present embodiment is not limited to the configuration shown in FIG. 10, and any configuration of the coupled line strip conductor 4 and the stub-like strip conductor 6 described in the above first to third embodiments may be applied. I will do it.

  In the example of FIG. 10, a filter formed by cascade-connecting the first to third high-frequency coupling lines is shown. However, the present invention is not limited to this, and only the first high-frequency coupling line is used. May be.

  In the present embodiment, the stub-shaped strip conductor has a length of 90 degrees at a frequency three times the design frequency f0, and the interdigital coupling line between the stub-shaped strip conductors has an electrical length of 270 degrees. Since the interdigital coupling line portion is equivalent to a distributed constant line having an electrical length of 270 degrees, this filter is represented by an equivalent circuit as shown in FIG. It operates as a band rejection filter corresponding to four stages. Therefore, in this filter, currency loss increases at a frequency three times the design frequency, and the frequency characteristics are as shown in FIG. As described above, according to the present embodiment, there is a feature that a band-pass filter having a good attenuation characteristic over a wide frequency range can be obtained with less unnecessary signal transmission on the high frequency side of the pass band.

  In the above description of the first to fourth embodiments, the microstrip line structure has been described for the sake of simplicity, but other line forms such as a strip line, a coplanar line, and the like have been described. It goes without saying that the same effect can be expected in either case.

It is a perspective view of the microstrip line type | mold coupling line in Embodiment 1 of this invention. It is an equivalent circuit of the coupled line in Embodiment 1 of this invention. FIG. 5 is a circuit diagram for explaining the operation of the present coupled line at a frequency three times the design frequency, which is an equivalent circuit of the coupled line in the first embodiment of the present invention. It is explanatory drawing which shows the rough frequency characteristic of the coupling line in Embodiment 1 of this invention with a graph. It is a perspective view of the microstrip line type | mold coupling line in Embodiment 2 of this invention. It is an equivalent circuit of the coupling line in Embodiment 2 of this invention. It is a perspective view of the microstrip line type | mold coupling line in Embodiment 3 of this invention. It is an equivalent circuit of the coupled line in Embodiment 3 of this invention. It is explanatory drawing which shows the frequency characteristic of the coupling line in Embodiment 3 of this invention with a graph. It is a perspective view of the microstrip line type band pass filter in Embodiment 4 of the present invention. It is the equivalent circuit of the filter of Embodiment 4 of this invention. It is explanatory drawing which shows the rough frequency characteristic of the filter of Embodiment 4 of this invention with a graph. It is a perspective view of the conventional microstrip line type | mold coupling line. It is a figure which shows the frequency characteristic of the conventional coupling line.

Explanation of symbols

  1 dielectric substrate (dielectric layer), 2 ground conductors, 3a, 3b input / output strip conductors, 4a, 4b, 4-1a, 4-2a, 4-2b, 4-1b, 4-2b, 4-3b coupling Line strip conductors, 5,5-1, 5-2, 5-3 conductor gaps, 6, 6-1a, 6-2a, 6-3a, 6-1b, 6-2b, 6-3b stub-shaped strip conductors, 7a, 7b, 7-1a, 7-2a, 7-3a, 7-1b, 7-2b, 7-3b Open end, 8a, 8b Open end, 9a, 9b Connection part, 10 2 terminal circuit coupling line part.

Claims (3)

A pair of two-terminal circuit coupling line sections each having one end as a short-circuited end or an open end and two distributed constant lines having input / output terminals at the other end arranged in parallel and electromagnetically coupled to each other; ,
And one or more stub-shaped distributed constant lines having one end as a short-circuited end or an open end,
The stub-shaped distributed constant line is arranged substantially parallel to and in close proximity to the distributed constant line constituting the two-terminal circuit coupling line portion,
RF coupling line, characterized in that the other end of the stub-like distributed constant line, connected to the distribution the other end part near portion of the entering output terminal side of the constant lines constituting the two-terminal circuit coupling line part. The two distributed constant lines constituting the two-terminal circuit coupling line portion are arranged in opposite directions,
Both the distributed constant line and the stub-like distributed constant line have substantially the same electrical length of less than 90 degrees at the design frequency,
The stub-shaped distributed constant line is attached to at least one of the distributed constant lines, and the attachment position is a portion near the other end on the input / output terminal side of the distributed constant line. The high frequency coupling line according to claim 1 . High-frequency filter, characterized in that configured by a plurality cascaded RF coupling line according to claim 1 or 2.

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