CN115765420A - Switching switch circuit and control method thereof - Google Patents
Switching switch circuit and control method thereof Download PDFInfo
- Publication number
- CN115765420A CN115765420A CN202211621746.5A CN202211621746A CN115765420A CN 115765420 A CN115765420 A CN 115765420A CN 202211621746 A CN202211621746 A CN 202211621746A CN 115765420 A CN115765420 A CN 115765420A
- Authority
- CN
- China
- Prior art keywords
- bypass switch
- switch
- bypass
- current
- slave
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 238000000034 method Methods 0.000 title claims abstract description 30
- 238000005070 sampling Methods 0.000 claims abstract description 46
- 239000003990 capacitor Substances 0.000 claims abstract description 22
- 230000000630 rising effect Effects 0.000 claims description 5
- 239000004065 semiconductor Substances 0.000 claims description 3
- 230000008569 process Effects 0.000 abstract description 16
- 238000010586 diagram Methods 0.000 description 12
- 230000008859 change Effects 0.000 description 4
- 238000007599 discharging Methods 0.000 description 3
- 230000010355 oscillation Effects 0.000 description 3
- 230000001960 triggered effect Effects 0.000 description 3
- 230000003321 amplification Effects 0.000 description 2
- 238000013461 design Methods 0.000 description 2
- 230000005669 field effect Effects 0.000 description 2
- 238000012423 maintenance Methods 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 238000003199 nucleic acid amplification method Methods 0.000 description 2
- 230000003071 parasitic effect Effects 0.000 description 2
- 238000010521 absorption reaction Methods 0.000 description 1
- 230000009471 action Effects 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 230000009977 dual effect Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 238000011156 evaluation Methods 0.000 description 1
- 230000035772 mutation Effects 0.000 description 1
- 230000004044 response Effects 0.000 description 1
Images
Landscapes
- Power Conversion In General (AREA)
Abstract
The invention discloses a switching switch circuit and a control method thereof, wherein the switching switch circuit comprises a slave bypass and a main bypass, the slave bypass is connected with the main bypass in parallel, a slave bypass switch, a current limiting element and a sampling element are arranged on the slave bypass in series, and a main bypass switch is arranged on the main bypass; the first driving module is connected with the slave bypass switch, and the second driving module is connected with the master bypass switch. The charging current of the input capacitor of the power module is limited through the current limiting element, the voltage or the current acquired by the sampling element end is judged to be lower than a set threshold value, the second driving module outputs a slowly-rising driving signal to the main bypass switch, the voltage of the main bypass switch slowly rises until the voltage is stable, the power end voltage is kept stable in the process of switching in or switching out the power module, and the circuit element is effectively protected.
Description
Technical Field
The invention relates to the technology of power electronic circuits, in particular to a switching switch circuit and a control method thereof.
Background
China's coastline is lengthy, and the underwater marine engineering equipment can not be left for protecting and developing marine underwater resources. The underwater special power supply provides high-reliability high-quality power supply for the marine underwater engineering equipment, and is marine underwater core engineering equipment. Because the marine underwater environment is special, and the maintenance of the underwater special power supply is extremely difficult, the reliability design requirement of the underwater special power supply is extremely high. The input power of the underwater special power supply comes from shore-based high-voltage direct current, the parasitic parameters of a submarine cable line are large, and the working impact of a load is strong, so that the voltage at the input end of the underwater special power supply fluctuates widely. Therefore, the underwater special power supply adopts a mode of multi-power module input series connection and output parallel connection (ISOP), namely the underwater special power supply adopts a mode of a plurality of power modules arranged in series connection, and each power module shares a part of input voltage. Meanwhile, in order to ensure high reliability, a certain number of redundant power modules need to be reserved, and the input ends of the reserved redundant power modules are connected in series with the power modules which are put into use. In the power supply operation process, the switching-in and switching-out of the power module need to be controlled.
Because the parasitic parameters of a long-distance transmission submarine cable line are large, the voltage of the input end of an underwater power supply can be changed in a wide range from full load to no load, and the output of the underwater special power supply is required to be stable in a wide-range change, so that the quantity of power modules connected in series needs to be adjusted according to the range of the input voltage to ensure that the input voltage of the power modules is in a reasonable range. If the input voltage of the power module is too high, the power device bears too high voltage, and the reliability is reduced; if the input voltage of the power module is too low, the output voltage of the power supply cannot be stabilized at a rated value. The regulation of the number of power modules connected in series is usually carried out by a switching circuit. When the input voltage is increased, more power modules need to be put into the power supply in order to control the voltage of the input end of each power module within an allowable range, and when the input voltage is reduced, a part of power modules need to be cut out in order to ensure the voltage of the input end of the power supply to be stable. Furthermore, power modules that fail unrecoverably need to be permanently switched out. During the switching-in or switching-out process of the power module, the power output needs to be kept stable. Namely, the switching-in and switching-out of the power module need to be dynamically carried out, and the switching-in and switching-out can not be stopped.
In order to realize the consistency of the expected service lives of all the power modules, the redundant power modules adopt a control scheme with consistent service duration, and the alternate operation is realized through the switching switch circuit and the control method thereof.
When the switching switch circuit is conducted, the power module connected with the switching switch circuit in parallel is switched out; the switching switch circuit is closed, and the power module connected with the switching switch circuit in parallel is put into operation. The working reliability of the switching switch circuit directly influences the working reliability of the underwater special power supply system.
FIG. 1 is a schematic diagram of the input capacitance charging current flow for a cut-out process according to the prior art of the present invention; the prior art has the following disadvantages: when the module is switched out, the bypass switch is conducted, the voltage of the switched-out power module end is zero, so that the input end of the power supply charges the input capacitor of the switched-in power module, and because the internal resistance of the input capacitor is very small, a large impact current flows through the bypass switch and far exceeds the range which can be borne by a power electronic power device, and the damage and the failure of the bypass switch or the anti-reverse diode are caused. The input end voltage of the input power module is rapidly changed due to the overlarge impact current, impact is caused to the input voltage-sharing adjusting ring of the power module, and input uneven voltage protection is easily triggered.
The prior patent document CN111740604A discloses a dc converter for subsea power supply and a control method thereof, wherein the dc converter uses a general-purpose power electronic power device as a bypass switch, and 2 bypass switches connected in series are connected in parallel at an input end of a power module. When the switch is switched on, the power module connected in parallel with the switch is switched off, and when the switch is switched off, the power module connected in parallel with the switch is switched on. The inventors found that the disadvantages of this method are: (1) When the power module is switched out, the bypass switch is conducted, the input capacitors of other power modules are charged, and the input capacitors are very small in internal resistance and very large in instantaneous charging current and are likely to exceed the maximum current allowed by the bypass switch, so that the bypass switch is damaged; (2) The excessive instant charging current causes the voltage at each power module to change rapidly, interference and impact are caused to an input voltage-sharing control loop of the power modules connected in series, uneven voltage indexes exceed standards or oscillation is caused, the problem of unbalance of the voltage at the input end of a power supply is easily triggered, and the reliability of a system is influenced.
Disclosure of Invention
Aiming at the defects of the prior art, the invention aims to provide a switching switch circuit and a control method thereof, which solve the problems of damage of a bypass switch and unbalanced voltage of a power supply input end caused by overlarge instantaneous charging current when a power module is switched in or switched out.
In order to realize the purpose, the invention adopts the following technical scheme:
a switching switch circuit comprises a slave bypass, a master bypass, a first driving module and a second driving module, wherein the slave bypass is connected with the master bypass in parallel, a slave bypass switch, a current limiting element and a sampling element are arranged on the slave bypass in series, and a master bypass switch is arranged on the master bypass; the first driving module is connected with the slave bypass switch and used for controlling the slave bypass switch to be switched on or switched off, and the second driving module is connected with the main bypass switch and used for controlling the main bypass switch to be switched on or switched off.
Further, the slave bypass switch and the master bypass switch each include a three-terminal semiconductor device.
Further, a control electronic terminal of the slave bypass switch is connected with one end of the first driving module, an electron emission terminal of the slave bypass switch is connected with one end of the sampling element, and an electron receiving terminal of the slave bypass switch is connected with one end of the current limiting element; the control electronic end of the main bypass switch is connected with the first end of the second drive module, the other end of the first drive module, the other end of the sampling element and the second end of the second drive module are connected with the electronic emission end of the main bypass switch together, the other end of the current limiting element is connected with the electronic receiving end of the main bypass switch, and the third end of the second drive module is connected between the auxiliary bypass switch and the sampling element.
Furthermore, diodes are connected in parallel between the electron emitting ends and the electron receiving ends of the slave bypass switch and the master bypass switch, the input ends of the diodes are connected with the electron emitting ends, and the output ends of the diodes are connected with the electron output ends.
Further, the current limiting element includes a current limiting resistor.
Further, the resistance of the current limiting resistor is selected to ensure that the current from the bypass is less than 0.6 times the maximum current allowed to pass from the collector terminal of the bypass switch.
Further, the sampling element includes a current sampling resistor.
A control method based on a switching switch circuit comprises the following steps:
the first driving module controls the conduction of the slave bypass switch; the current limiting element limits the charging current of the input capacitor of the power module, and prevents the charging current from excessively endangering the slave bypass switch;
judging whether the voltage or the current acquired by the sampling element exceeds a set threshold range or not;
when the current value or the voltage value acquired by the sampling element exceeds a set threshold range, the second driving module outputs a slowly rising driving signal to the main bypass switch;
the voltage between the electron emission end and the electron receiving end of the main bypass switch slowly rises until the voltage is stable.
The utility model provides an adopt many power module circuit of on-off switch circuit, including input power and with a plurality of power module of input power series connection, it is single power module includes on-off switch circuit, input end circuit and DC/DC converter, and the on-off switch circuit, input end circuit and DC/DC converter connect the setting in parallel between the three, be provided with input capacitance on the input end circuit.
Further, the maximum current allowed to pass through the collector terminal of the main bypass switch is at least twice the maximum input current when the multiple power modules are operated in series.
The invention has the beneficial effects that:
the invention can effectively inhibit the instant charging current in the switching process, protect the bypass switch, has easy evaluation of switching time and fast response speed, reduces the range of voltage disturbance of the input end of the series power module, avoids the interference on the input voltage-sharing control loop, can inhibit the voltage fluctuation rate of the input module end, prevents the interference and the impact on the input voltage-sharing control loop of the series power module, and ensures the stable dynamic switching process of the multi-power module and small disturbance.
Drawings
The accompanying drawings, which are incorporated in and constitute a part of this application, illustrate embodiments of the invention and, together with the description, serve to explain the invention and not to limit the invention. In the drawings:
FIG. 1 is a schematic diagram illustrating the input capacitor charging current flow during switching out of a power module according to the prior art;
FIG. 2 is a schematic diagram of a switching switch circuit topology according to an embodiment of the invention;
FIG. 3 is a schematic diagram of a multi-power module circuit topology according to an embodiment of the invention;
FIG. 4 is a timing diagram of slave and master bypass switch drive signals in the fling-cut switch circuits of the remaining series-connected power modules after the redundant power modules are switched out, according to an embodiment of the present invention;
FIG. 5 is a graph of voltage waveforms across a main bypass switch according to an embodiment of the present invention;
fig. 6 is a waveform diagram of currents of the slave bypass switch and the master bypass switch in the fling-cut switch circuit of the remaining series power modules after the redundant modules are cut out according to the embodiment of the present invention.
Reference numerals are as follows: 1. a current limiting resistor; 2. a slave bypass switch; 3. a current sampling resistor; 4. a main bypass switch; 5. a first driving module; 6. and a second driving module.
Detailed Description
It should be noted that the embodiments and features of the embodiments in the present application may be combined with each other without conflict. The present invention will be described in detail below with reference to the embodiments with reference to the attached drawings.
In order to make the technical solutions of the present invention better understood, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be obtained by a person skilled in the art without making any creative effort based on the embodiments in the present invention, shall fall within the protection scope of the present invention.
It should be noted that the terms "first," "second," and the like in the description and claims of the present invention and in the drawings described above are used for distinguishing between similar elements and not necessarily for describing a particular sequential or chronological order. It is to be understood that the data so used may be interchanged under appropriate circumstances in order to facilitate the description of the embodiments of the invention herein. Moreover, the terms "comprises," "comprising," and "having," and any variations thereof, are intended to cover a non-exclusive inclusion, such that a process, method, system, article, or apparatus that comprises a list of steps or elements is not necessarily limited to those steps or elements expressly listed, but may include other steps or elements not expressly listed or inherent to such process, method, article, or apparatus.
The embodiment mainly solves 2 difficult problems in the switching process of the power module.
(1) Difficulty 1: when the switching switch is switched off, the switching switch is directly switched on, one power module is switched off due to the fact that a plurality of power modules input in series are connected, the series total voltage of the power modules is different from the power input voltage, the power input voltage can charge the input capacitor of each input power module, the input voltage of the input power module is raised, at the moment, a large impact current can be generated (because the content of the input capacitor is small), the impact current can easily exceed the current limit allowed by the switching switch, and the switching switch is damaged.
(2) Difficulty 2: the input end voltage of the input power module is rapidly raised due to the overlarge impact current, the rising rate of the input end voltage may exceed the adjusting frequency of a voltage-sharing control loop, voltage-sharing control failure or oscillation is caused, voltage imbalance occurs in the input end voltage of each input power module, and uneven voltage protection is triggered or overvoltage damage is caused to the module.
In this embodiment, a switching switch circuit is provided, fig. 2 is a schematic diagram of a topological structure of the switching switch circuit according to an embodiment of the present invention, and as shown in fig. 2, the structure includes a slave bypass, a master bypass, a first driving module 5 and a second driving module 6, the slave bypass is connected in parallel with the master bypass, a slave bypass switch 2, a current limiting element and a sampling element are connected in series on the slave bypass, the current limiting element is used for limiting a charging current of an input capacitor, the sampling element is used for reflecting a current or voltage condition of the slave bypass, and a master bypass switch 4 is arranged on the master bypass; the first driving module 5 is connected with the slave bypass switch 2 and used for controlling the slave bypass switch 2 to be switched on or switched off, and the second driving module 6 is connected with the main bypass switch 4 and used for controlling the main bypass switch 4 to be switched on or switched off. The current limiting element comprises a current limiting resistor 1 and the sampling element comprises a current sampling resistor 3. The slave bypass switch 2 and the master bypass switch 4 each comprise a three-terminal semiconductor device, which may be a triode or a field effect transistor or a high voltage IGBT device, or the like.
According to the switching switch circuit structure, the first driving module 5 controls the conduction of the slave bypass switch 2 to charge the input capacitor of the power module, and the current limiting element can effectively prevent the safety of the slave bypass switch 2 and the master bypass switch 4 from being endangered by overhigh instant charging current generated when the input capacitor charges are redistributed, so that the reliability of the system is improved; further acquiring the current condition flowing through the sampling element, and judging whether the voltage value or the current value acquired by the sampling element is lower than a set threshold value or not; when the voltage value is lower than the set threshold value, the second driving module 6 outputs a driving signal to the main bypass switch 4, so that the voltage between the electronic transmitting end and the electronic receiving end of the main bypass switch 4 rises, and the voltage value always belongs to the range of the voltage value allowed by the input end of the power module.
In this embodiment, the corresponding power module switching system will not work after the main bypass is turned on, and if the switching switch circuit only has the main bypass, a large impact current is generated in the switching process, and the main bypass power switch device will be damaged. The secondary bypass is connected with the current-limiting resistor 1 in series, so that the impact current can be limited, the current-limiting charging and discharging of the input capacitor can be realized, and the overlarge impact can be avoided. After the auxiliary bypass is opened, the input capacitor is charged and discharged to a certain degree (judged by a sampling element on the auxiliary bypass) and then the main bypass switch is switched on to realize the switching-out function, if the switching switch circuit only has the auxiliary bypass, the system input current completely flows through the current limiting resistor 1 of the auxiliary bypass, the power grade of the required resistor is very large (the power is equal to the square of the input current multiplied by the current limiting resistance value), and the efficiency of the underwater power supply system is extremely low.
In this embodiment, the threshold refers to a current value or a voltage value, and the threshold is set according to actual conditions.
In the embodiment, the control electronic end of the bypass switch 2 is connected with one end of the first driving module 5, the electronic emitting end of the bypass switch 2 is connected with one end of the sampling element, and the electronic receiving end of the bypass switch 2 is connected with one end of the current limiting element; the control electronic end of the main bypass switch 4 is connected with the first end of the second drive module 6, the other end of the first drive module 5, the other end of the sampling element and the second end of the second drive module 6 are connected with the electronic emission end of the main bypass switch 4, the other end of the current limiting element is connected with the electronic receiving end of the main bypass switch 4, and the third end of the second drive module 6 is connected between the slave bypass switch 2 and the sampling element.
The current-limiting resistor value is large, the main function is current limiting, and the resistance value of the sampling element (resistor) is small, as shown in fig. 2, in this embodiment, the connection sequence of the bypass switch 2, the current-limiting resistor 1 and the current sampling resistor 3 is optimal, because the driving of the main bypass switch 4 and the driving of the slave bypass switch 2 can be grounded with the input end of the power module, the design is simplified.
The first driving module 5 and the second driving module 6 both have one end connected to the bypass switch, which is a driving signal of the bypass switch: the bypass switch is turned on at a high level and turned off at a low level or a negative level. The other ends of the first driving module 5 and the second driving module 6 are grounded, and the third end of the second driving module 6 is connected with the sampling element and is used for detecting the voltage or the current of the sampling element, so as to judge the charging and discharging degree and determine whether the conduction of the main bypass switch 4 can be started or not.
The slave bypass switch 2 and the master bypass switch 4 may be a triode or a field effect transistor or a high voltage IGBT device.
The current grade of the high-voltage MOSFET is generally small, and the selection is difficult. In this embodiment, a high-voltage IGBT device is preferably used, and a corresponding connection manner is provided, specifically as follows:
the grid of the secondary bypass switch 2 is connected with one end of the first driving module 5, the emitter of the secondary bypass switch 2 is connected with one end of the sampling element, and the collector of the secondary bypass switch 2 is connected with one end of the current limiting element; the grid of the main bypass switch 4 is connected with one end of the second driving module 6, the other end of the first driving module 5, the other end of the sampling element and the second end of the second driving module 6 are connected with the transmitting end of the main bypass switch 4, and the other end of the current limiting element is connected with the current collection set of the main bypass switch 4.
The IGBT has three terminals: a collector for emitting electrons, an emitter for controlling electrons (so that the current flow to the collector is controlled by the base input signal), and a gate for collecting electrons.
In this embodiment, the current limiting element includes a current limiting resistor 1, and provides the selection condition of the current limiting resistor 1:
the resistance value of the current limiting resistor 1 is selected to ensure that the maximum impact current is less than 0.6 time of the maximum current allowed from the collecting electronic end of the bypass switch 2, the selection is based on the relevant standard, the I-level derate is 0.6, the II-level derate is 0.7, the operation and maintenance difficulty of the underwater power supply is high, and therefore the I-level derate is selected. Wherein the rush current is the instantaneous charging current of the input capacitor.
In the present example, the sampling element comprises a current sampling resistor 3. The current sampling resistor 3 can reflect the current flowing through the current sampling resistor 3.
Through current sampling resistor 3, detect the electric current that flows through from bypass switch 2, compare the magnitude of the electric current value that obtains and threshold value that will detect, control leading bypass switch 4 according to the comparison result and switch on, avoid following bypass switch 2 conduction time overlength, current-limiting resistor 1 is overheated, combines drive signal to slowly rise the strategy simultaneously, avoids main bypass switch 4 to appear the second rush current when switching on. The reliability of the main bypass switch 4 and the slave bypass switch 2 is effectively guaranteed, namely, the effectiveness of the fling-cut switch circuit is guaranteed.
As another fling-cut switch circuit in this embodiment, a diode is connected in parallel between the electron emitting end and the electron receiving end of the slave bypass switch 2 and the main bypass switch 4, the input end of the diode is connected with the electron emitting end, and the output end of the diode is connected with the electron output end. In this embodiment, the diode is a body diode inside the IGBT device.
In this embodiment, a method for controlling a switching switch circuit is further provided, including:
s01, the first driving module 5 controls the slave bypass switch 2 to be conducted; the current limiting element limits the charging current of the input capacitor of the power module, and prevents the secondary bypass switch 2 from being endangered by the excessive charging current;
s02, judging whether the current or the voltage acquired by the sampling element is lower than a set threshold value;
s03, when the current or the voltage acquired by the sampling element is lower than a set threshold, the second driving module 6 outputs a slowly rising driving signal to the main bypass switch 4;
and S04, slowly increasing the voltage between the electron emitting end and the electron receiving end of the main bypass switch 4, and slowly increasing the voltage between the electron emitting end and the electron receiving end of the main bypass switch 4 until the voltage is stable.
Regarding the threshold setting: the current is large in the switching-out process, the current is gradually reduced along with the charging and discharging of the input capacitor (see fig. 6), and when the current is larger than but close to the system input current, the main bypass switch 4 already has the conducting condition.
The embodiment further comprises a main controller, wherein the main controller sends a signal switched into or out of the power module to the first driving module 5, and when the signal is received, the first driving module 5 outputs a high level to control the conduction of the slave bypass switch 2. And a threshold value is set at the main controller end, the sampling element feeds back the acquired voltage or current to the main controller, and when the voltage or current is lower than the set threshold value, the main controller sends a signal to enable the second driving module 6 to output a slowly-rising driving signal.
In this embodiment, a multi-power module circuit using a switching switch circuit is further provided, and fig. 3 is a schematic diagram of a topology structure of the multi-power module circuit according to the embodiment of the present invention, as shown in fig. 3, the structure includes:
the power module comprises an input power supply and a plurality of power modules connected with the input power supply in series, wherein each power module comprises a switching switch circuit, an input end circuit and a DC/DC converter, the switching switch circuit, the input end circuit and the DC/DC converter are arranged in parallel, and an input capacitor is arranged on the input end circuit. A diode is arranged on a circuit between the power module and the input end circuit, and current flows out of the power module, enters the input end of the diode, flows out of the output end of the diode and then respectively flows into the input end circuit and the DC/DC converter.
The embodiment also provides the selection conditions of the main bypass switch 4:
the maximum current value allowed by the collecting terminal end of the main bypass switch 4 at least exceeds twice of the maximum input current value when the multiple power modules work in series, and I-level derating is met.
The contents of the above embodiments will be described with reference to a preferred embodiment.
Fig. 2 is a schematic diagram of a circuit topology of a fling-cut switch according to an embodiment of the present invention, and as shown in fig. 2, the circuit topology includes: the slave bypass circuit comprises a current limiting resistor 1, a slave bypass switch 2 and a current sampling resistor 3 which are connected in series, wherein the collector of the slave bypass switch 2 is connected with the current limiting resistor 1, and the emitter is connected with the current sampling resistor 3. The main bypass is formed by a main bypass switch 4, and the main bypass is connected in parallel with the slave bypass switch 2. The first driving module 5 controls the on and off of the slave bypass switch 2, and the second driving module 6 controls the on and off of the master bypass switch 4. The main bypass switch 4 and the auxiliary bypass switch 2 are both high-voltage IGBT devices.
The control process of the switching switch circuit is as follows:
when the power module needs to be switched out, the first driving module 5 receives a switching-out signal transmitted by a main control module and then outputs a high level to control the conduction of the bypass switch 2, the current limiting resistor 1 limits the charging current of input capacitors of all power modules which are put into operation, the bypass switch is effectively prevented from being endangered by overlarge impact current, meanwhile, the fluctuation range of the input end voltage of the power modules which are put into operation is reduced by the aid of the slow charging current, disturbance of voltage mutation on an input equalizing ring is effectively avoided, loop oscillation is caused, and uneven voltage protection is achieved. As shown in fig. 4, fig. 4 is a timing diagram of the slave bypass switch driving signal and the master bypass switch driving signal in the fling-cut switch circuit in the remaining series-connected power modules after the redundant power modules are cut out according to the embodiment of the present invention.
When the current of the current sampling resistor 3 is lower than the set threshold, the second driving module 6 provides a ramp-up driving signal to the main bypass switch 4, as shown in fig. 5, where the abscissa is time t and the ordinate is voltage V, V GS Is the gate to emitter voltage. Fig. 5 is a graph of a voltage waveform across the main bypass switch 4 according to an embodiment of the present invention, where the voltage between the gate and the emitter of the main bypass switch 4 is slowly raised to achieve current limiting by extending the time that the power device passes through the amplification region (the device has a larger body resistance in the amplification region). The driving signal sent by the second driving module 6 has the characteristic of slow rise and can be realized by a larger gate driving resistor. The process of realizing the IGBT conduction is as follows: the high level (generally 12 to 18vdc, usually 15 VDC) charges the input capacitance through the gate of the IGBT, and the IGBT starts to conduct when the gate voltage exceeds its conduction threshold. A larger gate resistance can extend the time for the gate voltage to rise, achieving slow conduction (see fig. 5).
In the switching-out process, the waveforms of the currents flowing through the slave bypass switch 2 and the master bypass switch 4 are shown in fig. 6, where the abscissa is time t, the abscissa is seconds, the ordinate is current I, and the ordinate is amperes a. Fig. 6 is a diagram of current waveforms of the slave bypass switch 2 and the master bypass switch 4 of the fling-cut switch circuit in the remaining series power modules after the redundant modules are cut out according to the embodiment of the present invention. The impact current is obviously clamped, and the stability and reliability of cutting are ensured. In the switching process, as shown in fig. 4, due to the existence of the input capacitor of the switching power module, the clamping absorption function is achieved, the main bypass switch 4 and the slave bypass switch 2 are both turned off, the corresponding power module is put into use, and the loss of the simultaneous turning-off (low-level turning-off) of the main bypass switch 4 and the slave bypass switch 2 is very small and is zero-voltage turning-off.
Fig. 3 is a schematic diagram of a multi-power module circuit topology according to an embodiment of the invention.
The structure includes:
the power module comprises an input power supply and a plurality of power modules connected with the input power supply in series, wherein each power module comprises a switching switch circuit, an input end circuit and a DC/DC converter, and the switching switch circuit, the input end circuit and the DC/DC converter are arranged in parallel. An input capacitor is arranged on the input circuit. A diode is arranged on a circuit between the power module and the input end circuit, and current flows out of the power module, enters the input end of the diode, flows out of the output end of the diode and then flows into the input end circuit and the DC/DC converter respectively.
At any one time, only one power module performs the switching-out action. The method specifically comprises the following steps:
the underwater special power supply adopts a multi-power module input-series output parallel mode, and in order to adapt to a wide input voltage fluctuation range, the input-series multi-power modules need to be switched in or out:
when the input voltage is increased and the voltage of the input end of the single power module is close to the upper limit threshold value, 1 power module is required to be put into use to share the input voltage so as to ensure that the voltage of the input end of the power module is not overvoltage;
when the input voltage is reduced and the voltage of the input end of the single power module is close to the lower limit threshold value, 1 power module needs to be switched out, so that the voltage of the input end of the power module is prevented from being undervoltage, and the output voltage is prevented from being dropped.
In the embodiment, the impact of simultaneously switching a plurality of power modules on the underwater power supply system is large, so that only one power module is switched at any time in the switching process, and if a plurality of power modules are required to be switched, the power modules can be sequentially and continuously switched.
Therefore, in this embodiment, the slave bypass switch 2 is turned on first, the maximum value of the inrush current is clamped due to the existence of the current limiting resistor 1, and meanwhile, the slow rising driving signal is adopted when the main bypass switch 4 is turned on, so that the dual protection measures of the slave bypass and the main bypass are implemented, and the problem 1 is effectively solved. Indirectly, because the impact current is elongated on a time axis and the amplitude is suppressed, the terminal voltage change of the input power module is slowed down, the loop out of control caused by rapid change is avoided, and the problem 2 is effectively solved.
Various other modifications and changes may be made by those skilled in the art based on the above-described technical solutions and concepts, and all such modifications and changes should fall within the scope of the claims of the present invention.
Claims (10)
1. The switching switch circuit is characterized by comprising a slave bypass, a master bypass, a first driving module (5) and a second driving module (6), wherein the slave bypass is connected with the master bypass in parallel, a slave bypass switch (2), a current limiting element and a sampling element are arranged on the slave bypass in series, and a master bypass switch (4) is arranged on the master bypass; the first driving module (5) is connected with the auxiliary bypass switch (2) and used for controlling the auxiliary bypass switch (2) to be connected or disconnected, and the second driving module (6) is connected with the main bypass switch (4) and used for controlling the main bypass switch (4) to be connected or disconnected.
2. A fling-cut switch circuit according to claim 1, wherein the slave bypass switch (2) and the master bypass switch (4) each comprise a three-terminal semiconductor device.
3. The switching switch circuit according to claim 2, wherein a control electronic terminal of the slave bypass switch (2) is connected to one terminal of the first driving module (5), an electronic emission terminal of the slave bypass switch (2) is connected to one terminal of the sampling element, and an electronic receiving terminal of the slave bypass switch (2) is connected to one terminal of the current limiting element; the electronic control end of the main bypass switch (4) is connected with the first end of the second driving module (6), the other end of the first driving module (5), the other end of the sampling element and the second end of the second driving module (6) are connected with the electronic emission end of the main bypass switch (4), the other end of the current limiting element is connected with the electronic receiving end of the main bypass switch (4), and the third end of the second driving module (6) is connected between the auxiliary bypass switch (2) and the sampling element.
4. The switching switch circuit according to claim 2, wherein diodes are connected in parallel between the electron emitting terminals and the electron receiving terminals of the slave bypass switch (2) and the master bypass switch (4), the input terminals of the diodes are connected to the electron emitting terminals, and the output terminals of the diodes are connected to the electron receiving terminals.
5. The switching circuit according to claim 1, wherein said current limiting element comprises a current limiting resistor (1).
6. A switching switch circuit according to claim 5, characterized in that the value of the limiting resistor (1) is chosen to ensure that the current from the bypass is less than 0.6 times the maximum current allowed to pass from the collector terminal of the bypass switch (2).
7. The switching circuit according to claim 1, wherein said sampling element comprises a current sampling resistor (3).
8. A method for controlling a fling-cut switch circuit according to any one of claims 1-7, comprising:
the first driving module (5) controls the conduction of the slave bypass switch (2); the current limiting element limits the charging current of the input capacitance of the power module, preventing said charging current from endangering said slave bypass switch (2) too much;
judging whether the current or the voltage acquired by the sampling element exceeds a set threshold range;
when the current value or the voltage value acquired by the sampling element exceeds a set threshold range, the second driving module (6) outputs a slowly rising driving signal to the main bypass switch (4);
the voltage between the electron emission end and the electron receiving end of the main bypass switch (4) rises slowly until the voltage is stable.
9. A multi-power module circuit adopting the switching switch circuit as claimed in any one of claims 1 to 7, characterized by comprising an input power supply and a plurality of power modules connected in series with the input power supply, wherein a single power module comprises a switching switch circuit, an input end circuit and a DC/DC converter, the switching switch circuit, the input end circuit and the DC/DC converter are connected in parallel, and an input capacitor is arranged on the input circuit.
10. A multi-power module circuit according to claim 9, characterized in that the collecting terminal of the main bypass switch (4) allows a maximum current value to be passed which exceeds at least twice the maximum input current value of the multi-power modules when they are operated in series.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202211621746.5A CN115765420A (en) | 2022-12-16 | 2022-12-16 | Switching switch circuit and control method thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202211621746.5A CN115765420A (en) | 2022-12-16 | 2022-12-16 | Switching switch circuit and control method thereof |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN115765420A true CN115765420A (en) | 2023-03-07 |
Family
ID=85346340
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202211621746.5A Pending CN115765420A (en) | 2022-12-16 | 2022-12-16 | Switching switch circuit and control method thereof |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN115765420A (en) |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109546638A (en) * | 2018-10-22 | 2019-03-29 | 南京南瑞继保电气有限公司 | A kind of direct current energy-consuming device and control method |
| CN109742767A (en) * | 2019-03-04 | 2019-05-10 | 南京南瑞继保电气有限公司 | A kind of modularized dc energy-consuming device and control method |
| US20200067452A1 (en) * | 2018-08-24 | 2020-02-27 | Sungrow Power Supply Co., Ltd. | Active Bypass Control Device and Method for Photovoltaic Module |
| CN111740604A (en) * | 2020-06-04 | 2020-10-02 | 湖南大学 | DC converter for subsea power supply and control method thereof |
-
2022
- 2022-12-16 CN CN202211621746.5A patent/CN115765420A/en active Pending
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20200067452A1 (en) * | 2018-08-24 | 2020-02-27 | Sungrow Power Supply Co., Ltd. | Active Bypass Control Device and Method for Photovoltaic Module |
| CN109546638A (en) * | 2018-10-22 | 2019-03-29 | 南京南瑞继保电气有限公司 | A kind of direct current energy-consuming device and control method |
| CN109921453A (en) * | 2018-10-22 | 2019-06-21 | 南京南瑞继保工程技术有限公司 | Distributed energy-consuming device and module failure bypass control method |
| CN109742767A (en) * | 2019-03-04 | 2019-05-10 | 南京南瑞继保电气有限公司 | A kind of modularized dc energy-consuming device and control method |
| CN111740604A (en) * | 2020-06-04 | 2020-10-02 | 湖南大学 | DC converter for subsea power supply and control method thereof |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| EP3567711B1 (en) | Module of suppressing inrush current, method of controlling the same and on-board bidirectional charger using the same | |
| CN107086555B (en) | A kind of DC solid circuit breaker control method with adaptive throttling ability | |
| KR20210046782A (en) | DC energy consumption device and control method thereof | |
| CN101242136B (en) | Voltage source frequency converter bridge arm direct pass protector for three level integrated gate pole conversion transistor | |
| CN110739837B (en) | MMC power module adopting double bypass switches and overvoltage three bypass method | |
| CN101917156B (en) | Method and device for protecting wind generating set during electric network voltage dip in short time | |
| CN108075456B (en) | A kind of multi-functional fault current controllers and control method | |
| CN107863760B (en) | Current-limiting direct-current circuit breaker based on capacitance current conversion unit and control method thereof | |
| CN104426405A (en) | Modular multi-electric-level current converter and converter valve module unit thereof | |
| CN110429579B (en) | Reverse connection prevention protection circuit and method for improving safety and direct current power grid system | |
| US20210057911A1 (en) | Arrangement for regulating a power flow in an ac voltage grid and method for protecting the arrangement | |
| CN206619906U (en) | A kind of dc circuit breaker | |
| US20240014664A1 (en) | Power supply system and method for controlling output voltage of direct current combiner box | |
| CN115765420A (en) | Switching switch circuit and control method thereof | |
| CN113514762A (en) | System for detecting state of APF/SVG relay | |
| CN111092410A (en) | Hybrid solid-state circuit breaker and control method thereof | |
| CN201163716Y (en) | Short trouble current limiter with energy consumption resistor | |
| CN113162000B (en) | Improved self-adaptive current-limiting direct current solid-state circuit breaker and control method thereof | |
| CN114221318B (en) | MMC sub-module circuit topology structure, fault ride-through method and application thereof | |
| CN111211541B (en) | Direct current solid-state circuit breaker | |
| CN113839446A (en) | Intelligent capacitor pulse discharging device | |
| CN109861197B (en) | AC-proof grid-connected device for DC power supply system | |
| CN209344755U (en) | Low-voltage direct intelligent switch control system | |
| CN208299424U (en) | High-voltage circuitbreaker tripping coil delay protection device | |
| CN112491035A (en) | Direct current energy consumption device based on thyristor and control method thereof |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| RJ01 | Rejection of invention patent application after publication |
Application publication date: 20230307 |