CN108696137B - Modularized high-boost isolation type DC/DC converter with active clamping circuit - Google Patents
Modularized high-boost isolation type DC/DC converter with active clamping circuit Download PDFInfo
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- 230000003071 parasitic effect Effects 0.000 claims description 24
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The modularized high-boost isolation type DC/DC converter with the active clamping circuit has the advantages of small input current ripple, low transformer turn ratio and the like of the traditional L-type current input isolation type DC/DC converter, the input phase number can be adjusted in a modularized manner, the input and output voltage gain can be flexibly adjusted according to the number of diode capacitors of each module, and the modularized high-boost isolation type DC/DC converter can be suitable for application occasions with different power levels and boosting ratios. And each module realizes automatic current sharing, thereby simplifying the control strategy. By combining the active clamping circuit with the leakage inductance of the transformer, all the switching tubes realize zero-voltage switching on, the diodes realize zero-current switching off, and the reverse recovery loss of the diodes is suppressed. Meanwhile, compared with the existing high-boost technology, the voltage stress and the current stress of the main switch and the diode are reduced, and the method is applicable to occasions needing input and output electrical isolation.
Description
Technical Field
The invention relates to a direct current-direct current converter, in particular to a modularized high-boost isolation type DC/DC converter with an active clamping circuit.
Background
In recent years, the development of offshore wind power generation technology is rapid, and the offshore wind power direct current convergence technology is paid more attention and research due to the fact that the traditional alternating current convergence has a plurality of adverse factors such as high frequency synchronism and high harmonic content, but the technology is not mature due to the fact that the high-capacity high-boost DC/DC conversion technology. Direct current convergence is difficult to reach engineering practice.
In the face of continuously improving the capacity of a fan, under the voltage-withstanding and overcurrent capacity of the existing semiconductor switching device, the capacity expansion scheme of the converter is usually realized by serial-parallel connection of all sub-converters, and a large number of auxiliary circuits and control strategies are required to be additionally added during voltage equalizing and parallel connection in serial connection, so that the realization cost is high, the system construction is complex, and the reliability is insufficient.
Disclosure of Invention
Aiming at the technical problems, the invention provides a modularized high-boost isolation type DC/DC converter with an active clamping circuit, and the topological circuit of the converter has self-current equalizing capability, so that the problems of complex structure, high cost and the like of the existing modularized scheme can be effectively solved.
The technical scheme adopted by the invention is as follows:
a modularized high-boost isolation type DC/DC converter with active clamp circuit comprises a DC input power supply, m modules, a filter capacitor C 0 A load R L ；
The m modules comprise m power main switches VT 1 、VT 2 ...VT m The power main switch VT 1 、VT 2 ...VT m Corresponding drain-source parasitic capacitance C VT1 、C VT2 ...C VTm The method comprises the steps of carrying out a first treatment on the surface of the m clamping capacitors C C1 、C C2 、...C Cm The method comprises the steps of carrying out a first treatment on the surface of the m inductances L 1 、L 2 ...L m The method comprises the steps of carrying out a first treatment on the surface of the m transformation ratios are 1: high-frequency transformer T of k 1 、T 2 ...T m The high-frequency transformer T 1 、T 2 ...T m Corresponding leakage inductance L K1 、L K2 ...L Km The method comprises the steps of carrying out a first treatment on the surface of the nm capacitors C 11 、C 12 ...C nm The method comprises the steps of carrying out a first treatment on the surface of the m (n+2) diodes: d (D) 1 、D 2 、D 3 ...D m-1 、D m ，D 01 、D 02 、D 03 ...D 0(m-1) 、D 0m ，D 11 、D 12 、D 13 ...D 1(m-1) 、D 1m ，...D (n-1)1 、D (n-1)2 、D (n-1)3 ...D (n-1)(m-1) 、D (n-1)m ，D n 1 、D n 2 、D n 3 ...D n(m-1) 、D n m ；
The connection mode is as follows:
primary side end of module 1: inductance L 1 The other end of (a) is connected with a transformer T 1 Primary side homonymous terminal, first power master switch VT 1 Drain and the first of (2)A power auxiliary switch VT c1 Source of first power auxiliary switch VT c1 The drain electrode of (C) is connected with the clamping capacitor C c1 Is a member of the group;
secondary side end of module 1: transformer T 1 The secondary side homonymous terminal of (C) is connected with the capacitor C 11 One end of diode D 11 Anode and diode D of (c) 01 A cathode of (a); capacitor C 11 Is connected with the other end of the capacitor C 21 And diode D 21 An anode of (a); capacitor C 21 Is connected with the other end of the capacitor C 31 And diode D 31 An anode of (a); … and so on, capacitor C (n-1)1 Is connected with the other end of the capacitor C n1 And diode D (n-1)1 An anode of (a); capacitor C n1 And C at one end of (2) (n-1)1 The node between them is connected with diode D n1 Anode of (C), capacitance C n1 Is connected with the other end of diode D 1 An anode of (a);
primary side end of module 2: inductance L 2 The other end of (a) is connected with a transformer T 2 Primary side homonymous terminal, second power master switch VT 2 Is connected to the drain of the second power auxiliary switch VT c2 Source of a second power auxiliary switch VT c2 The drain electrode of (C) is connected with the clamping capacitor C c2 Is a member of the group;
secondary side end of module 2: transformer T 2 The secondary side homonymous terminal of (C) is connected with the capacitor C 12 One end of diode D 12 Anode and diode D of (c) 02 A cathode of (a); capacitor C 12 Is connected with the other end of the capacitor C 22 And diode D 22 An anode of (a); capacitor C 22 Is connected with the other end of the capacitor C 32 And diode D 32 An anode of (a); … and so on, capacitor C (n-1)2 Is connected with the other end of the capacitor C n2 And diode D (n-1)2 An anode of (a); capacitor C n2 And C at one end of (2) (n-1)2 The node between them is connected with diode D n2 Anode of (C), capacitance C n2 Is connected with the other end of diode D 2 An anode of (a);
and so on to module m:
primary side end of module m: inductance L m Is another of (1)One end is connected with the transformer T m Primary side homonymous terminal, mth power master switch VT m Drain of (d) and mth power master VT m The mth power master VT m The drain electrode of (C) is connected with the clamping capacitor C cm Is a member of the group;
secondary side end of module 2: transformer T m The secondary side homonymous terminal of (C) is connected with the capacitor C 1m One end of diode D 1m Anode and diode D of (c) 0m A cathode of (a); capacitor C 1m Is connected with the other end of the capacitor C 2m And diode D 2m An anode of (a); capacitor C 2m Is connected with the other end of the capacitor C 3m And diode D 3m An anode of (a); … and so on, capacitor C (n-1)m Is connected with the other end of the capacitor C nm And diode D (n-1)m An anode of (a); capacitor C nm And C at one end of (2) (n-1)m The node between them is connected with diode D nm Anode of (C), capacitance C nm Is connected with the other end of diode D m An anode of (a);
the connection mode among the modules is as follows:
negative electrode of direct current input power supply is grounded, and inductance L of module 1 1 One end is connected with the positive pole of the direct current input power supply, and the first power main switch VT 1 Source electrode is grounded, clamping capacitor C c1 The other end is grounded, the transformer T 1 Primary side heteronymous termination transformer T 2 Primary side synonym terminal and transformer T 1 Secondary side heteronymous termination transformer T 2 A secondary side heteronym terminal; diode D 11 Cathode D 22 Anode, diode D 21 Cathode joint D 32 Anode and so on to diode D n1 Cathode-connected diode D 2 Anode, diode D 1 Cathode load R L And filter capacitor C 0 Diode D 01 Is connected with the load R by the anode L And filter capacitor C 0 Is arranged at the other end of the tube;
inductance L of module 2 2 One end of the second power main switch VT is connected with the positive pole of the direct current input power supply 2 Source electrode is grounded, clamping capacitor C c2 The other end is grounded, the transformer T 2 Primary side heteronymous termination transformer T 3 Primary side synonym terminal and transformer T 2 Secondary side heteronymous termination transformer T 3 A secondary side heteronym terminal; diode D 12 Cathode D 23 Anode, diode D 22 Cathode joint D 33 Anode and so on to diode D n2 Cathode-connected diode D 3 Anode, diode D 2 Cathode load R L And filter capacitor C 0 Diode D 02 Is connected with the load R by the anode L And filter capacitor C 0 Is arranged at the other end of the tube;
and so on to module m:
inductance L of module m m One end is connected with the positive electrode of the power supply, and the mth power main switch VT m Source electrode is grounded, clamping capacitor C cm The other end is grounded, the transformer T m Primary side heteronymous termination transformer T 1 Primary side synonym terminal and transformer T m Secondary side heteronymous termination transformer T 1 A secondary side heteronym terminal; diode D 1m Cathode D 21 Anode, diode D 2m Cathode joint D 31 Anode and so on to diode D nm Cathode-connected diode D 1 Anode, diode D m Cathode load R L And filter capacitor C 0 Diode D 0m Is connected with the load R by the anode L And filter capacitor C 0 And the other end of (2).
The control mode is as follows: an interleaving control strategy is adopted between adjacent power switches; i.e. the switch drive phases between each adjacent two phases differ by 180. The auxiliary switches of each phase are complementarily conducted with the main switch, and enough dead time is reserved.
Compared with the prior isolation type technology, the modularized high-boost isolation type DC/DC converter with the active clamping circuit has the following beneficial effects:
1. the invention realizes the high boost output of the converter by utilizing the multi-boost unit, and the number of diodes and capacitors in each module is adjusted according to the requirement so as to change the gain. Compared with the prior art, the voltage stress of the power switch and the diode is also reduced, the gain of the converter is adjustable, the application range is wide, and the converter is more suitable for high-capacity and high-boost occasions. The transformer with lower turns ratio can be used for achieving the purpose of high boosting, and the design difficulty of the transformer is greatly reduced. Wherein:
the input/output gain is:
the voltage stress of the main switching tube is as follows:
the voltage stress of the diode in each module is:
wherein u is in For input voltage u 0 For output voltage, k is the number of turns of primary side on the secondary side turns ratio of the transformer, n is the number of capacitors of each module, m is the number of modules, and D is the duty ratio of the main switch. (i=1, 2,) n, j=1, 2,., m
2. When the duty ratio of each main switch is the same, each module can realize automatic current sharing due to the ampere-second balance of the capacitor, and each phase current of the secondary side is equalized to ensure that the current of the primary side flows through the transformer, the power of the transformer is equalized, no control strategy is needed to ensure current sharing, and compared with the traditional current sharing mode based on external detection, the circuit complexity is reduced, the circuit heat dissipation is easier to control, and the cost is greatly reduced.
3. The converter can adjust the number of input ports, namely the number of modules, according to different application occasions, can adapt to larger large-current input occasions, increases the capacity and automatically equalizes all the modules. The number of modules is adjusted, and the current stress of each module can be correspondingly changed, but the number of modules is required to be even. In each module:
the current stress of the main switching tube is as follows:
current of all diodes on secondary side shouldThe force is:
wherein D is the duty ratio of the main switch, m is the number of modules, I in For input current, n is the number of capacitors in each module, and k is the number of turns on the secondary side of the transformer compared with the number of turns on the primary side.
4. By adding the active clamping circuit, zero voltage turn-on of the switching tube and zero current turn-off of the diode are realized by utilizing leakage inductance of the transformer, loss is reduced, efficiency of the converter is improved, and influence of voltage spike of the switching tube caused by the leakage inductance of the transformer is limited.
Drawings
Fig. 1 is a schematic general diagram of the circuit of the present invention.
Fig. 2 is a topology of 4 modules of the modular high boost isolated DC/DC converter with active clamp circuit.
Fig. 3 shows the main switch VT when the converter m=4 and n=2 1 、VT 2 Simulation graphs of drive signal, voltage, current waveforms.
Fig. 4 shows the auxiliary switch VT when the converter m=4 and n=2 c1 、VT c2 Simulation graphs of drive signal, voltage, current waveforms.
Fig. 5 shows the clamp capacitance C when the converter m=4 and n=2 C1 、C C2 Voltage waveform and input voltage u in Output voltage u 0 Simulation of waveforms.
Fig. 6 shows the inductance L when the converter m=4 and n=2 1 、L 2 、L 3 、L 4 Simulation graphs of current waveforms.
Fig. 7 shows leakage inductance L when the converter m=4 and n=2 K1 、L K2 、L K3 、L K4 Simulation graphs of current waveforms.
Fig. 8 shows the capacitance C when the converter m=4 and n=2 11 、C 12 、C 13 、C 14 Simulation of voltage waveforms.
Fig. 9 shows a diode D when the converter m=4 and n=2 11 、D 12 Simulation graphs of voltage and current waveforms.
Fig. 10 shows the output diode D when the converter m=4 and n=2 1 、D 2 Simulation graphs of voltage and current waveforms.
Detailed Description
The invention is described in further detail below with reference to the attached drawings, examples of which:
as shown in FIG. 2, a 4-module modular high-boost isolated DC/DC converter with active clamp circuit comprises 1 DC input power source, 4 modules, 1 filter capacitor C 0 1 load R L . Each module comprises 1 power main switch, 1 power auxiliary switch, 1 clamping capacitor, 1 inductor, 1 high-frequency transformer, 4 diodes and 2 capacitors. Such that there are a total of 4 power master switches VT 1 、VT 2 、VT 3 、VT 4 Parasitic capacitance C of drain and source VT1 、C VT2 、C VT3 、C VT4 4 power auxiliary switches VT c1 、VT c2 、VT c3 、VT c4 4 clamping capacitors C c1 、C c2 、C c3 、C c4 4 inductances L 1 、L 2 、L 3 、L 4 The 4 transformation ratios are 1: high-frequency transformer T of k 1 、T 2 、T 3 、T 4 Leakage inductance L K1 、L K2 、L K3 、L K4 The secondary side end is provided with 8 capacitors C 11 、C 12 、C 13 、C 14 、C 21 、C 22 、C 23 、C 24 16 diodes D 1 、D 2 、D 3 、D 4 、D 01 、D 02 、D 03 、D 04 、D 11 、D 12 、D 13 、D 14 、D 21 、D 22 、D 23 、D 24 The method comprises the steps of carrying out a first treatment on the surface of the The connection mode of the 4 modules is as follows:
primary side end of module 1, inductance L 1 Is connected with the other end of the transformer T 1 Primary side homonymous terminal, first power master switch VT 1 Drain electrode and first work of (2)Rate auxiliary switch VT c1 Source, VT of (v) c1 The drain electrode of (C) is connected with the clamping capacitor C c1 Is provided. Module 1 secondary side end, transformer T 1 Secondary side homonymous terminal capacitor C 11 One end of diode D 11 Anode and diode D of (c) 01 Cathode of capacitor C 11 Is connected with the other end of the capacitor C 21 And diode D 21 Anode of (C), capacitance C 21 Another end connected with diode D 1 Is a positive electrode of (a).
Primary side end of module 2, inductance L 2 Is connected with the other end of the transformer T 2 Primary side homonymous terminal, second power master switch VT 2 Is connected to the drain of the second power auxiliary switch VT c2 Source, VT of (v) c2 The drain electrode of (C) is connected with the clamping capacitor C c2 Is provided. Module 2 secondary side end, transformer T 2 Secondary side homonymous terminal capacitor C 12 One end of diode D 12 Anode and diode D of (c) 02 Cathode of capacitor C 12 Is connected with the other end of the capacitor C 22 And diode D 22 Anode of (C), capacitance C 22 Another end connected with diode D 2 Is a positive electrode of (a).
Module 3 primary side end, inductance L 3 Is connected with the other end of the transformer T 3 Primary-side homonymous terminal, third power master switch VT 3 Is connected to the drain of the third power auxiliary switch VT c3 Source, VT of (v) c3 The drain electrode of (C) is connected with the clamping capacitor C c3 Is provided. Module 3 secondary side end, transformer T 3 Secondary side homonymous terminal capacitor C 13 One end of diode D 13 Anode and diode D of (c) 03 Cathode of capacitor C 13 Is connected with the other end of the capacitor C 23 And diode D 23 Anode of (C), capacitance C 23 Another end connected with diode D 3 Is a positive electrode of (a).
Module 4 primary side end, inductance L 4 Is connected with the other end of the transformer T 4 Primary side homonymous terminal, fourth power master switch VT 4 Is connected to the drain of the fourth power auxiliary switch VT c4 Source, VT of (v) c4 The drain electrode of (C) is connected with the clamping capacitor C c4 Is provided. Module 4 secondary side end, transformer T 4 Secondary side homonymous terminal capacitor C 14 One end of diode D 14 Anode and diode D of (c) 04 Cathode of capacitor C 14 Is connected with the other end of the capacitor C 24 And diode D 24 Anode of (C), capacitance C 24 Another end connected with diode D 4 Is a positive electrode of (a).
The connection mode among the modules is as follows:
the negative electrode of the power supply is grounded, and the inductance L of the module 1 1 One end is connected with the positive pole of the power supply, and the first power main switch VT 1 Source electrode is grounded, clamping capacitor C c1 The other end is grounded, the transformer T 1 Primary side heteronymous termination transformer T 2 Primary side synonym terminal and transformer T 1 Secondary side heteronymous termination transformer T 2 And a secondary side synonym terminal. Diode D 11 Cathode D 22 Anode, diode D 21 Cathode-connected diode D 2 Anode, diode D 1 Cathode load R L And filter capacitor C 0 Diode D 01 Is connected with the load R by the anode L And filter capacitor C 0 And the other end of (2).
Module 2 inductance L 2 One end is connected with the positive pole of the power supply, and the first power main switch VT 2 Source electrode is grounded, clamping capacitor C c2 The other end is grounded, the transformer T 2 Primary side heteronymous termination transformer T 3 Primary side synonym terminal and transformer T 2 Secondary side heteronymous termination transformer T 3 And a secondary side synonym terminal. Diode D 12 Cathode D 23 Anode, diode D 22 Cathode-connected diode D 3 Anode, diode D 2 Cathode load R L And filter capacitor C 0 Diode D 02 Is connected with the load R by the anode L And filter capacitor C 0 And the other end of (2).
Module 3 inductance L 3 One end is connected with the positive pole of the power supply, and the first power main switch VT 3 Source electrode is grounded, clamping capacitor C c3 The other end is grounded, the transformer T 3 Primary side heteronymous termination transformer T 4 Primary side synonym terminal and transformer T 3 Secondary side heteronymous termination transformer T 4 And a secondary side synonym terminal.Diode D 13 Cathode D 24 Anode, diode D 23 Cathode-connected diode D 4 Anode, diode D 3 Cathode load R L And filter capacitor C 0 Diode D 03 Is connected with the load R by the anode L And filter capacitor C 0 And the other end of (2).
Module 4 inductance L 4 One end is connected with the positive pole of the power supply, and the first power main switch VT 4 Source electrode is grounded, clamping capacitor C c4 The other end is grounded, the transformer T 4 Primary side heteronymous termination transformer T 1 Primary side synonym terminal and transformer T 4 Secondary side heteronymous termination transformer T 1 And a secondary side synonym terminal. Diode D 14 Cathode D 21 Anode, diode D 24 Cathode-connected diode D 1 Anode, diode D 4 Cathode load R L And filter capacitor C 0 Diode D 04 Is connected with the load R by the anode L And filter capacitor C 0 And the other end of (2).
The modularized high-boost isolation type DC/DC converter with the active clamping circuit is controlled by adopting an interleaving control strategy between adjacent power switches; i.e. the switch drive phases between each adjacent two phases differ by 180. The auxiliary switches of each phase are complementarily conducted with the main switch, and enough dead time is reserved.
To simplify the analysis process, assume: (1) 4 inductor currents are continuous; (2) the secondary side capacitance is large enough, and the upper voltage is kept unchanged; (3) all devices are ideal; (4) the resonance period between the clamping capacitor and the leakage inductance is far longer than the turn-off time of the switch, and the ripple wave on the clamping capacitor is ignored; (5) an interleaving control strategy is adopted between adjacent main switches; i.e. the main switch drive phase between each adjacent two phases differs by 180 ° and the duty cycle D >0.5; (6) the auxiliary switches are complementarily conducted with the main switches of the respective branches, and a sufficient dead time is reserved when the auxiliary switches are switched with the main switches.
According to the different power switch states, the circuit can be divided into 21 working states:
(1) The 4 power main switches are all on, the 4 power auxiliary switches are all off, and the input power supply is on at the momentOverpower switch VT 1 Power switch VT 2 Power switch VT 3 Power switch VT 4 Respectively to the inductance L 1 Inductance L 2 Inductance L 3 Inductance L 4 Charging; all diodes are turned off. Filter capacitor C 0 Discharging the load.
(2)VT 2 、VT 4 Drive signal off, VT 1 、VT 3 Keep on, inductance L 1 And inductance L 3 The current continues to rise, inductance L 2 And inductance L 4 Current to main switching tube VT 2 、VT 4 Drain-source parasitic capacitance C of (2) VT2 、C VT4 The charging, because of the influence of parasitic capacitance of the drain and the source, limits the rising speed of the drain and the source voltage, and can effectively reduce the turn-off loss; the process continues until the voltage on the drain-source parasitic capacitance rises to u 0 /(3k)。
(3) When the main switch tube VT 2 、VT 4 Drain-source parasitic capacitance C VT2 、C VT4 The voltage of (2) rises to u 0 At/(3 k), leakage inductance L K2 、L K4 The current of (c) starts to rise. Diode D is a diode because of the limited rate of rise of current through the transformer due to leakage inductance 12 、D 22 、D 2 、D 03 、D 14 、D 24 、D 4 、D 01 Approximately zero current conduction is achieved. The second side is the first loop, diode D 12 、D 22 、D 2 、D 03 、D 14 、D 24 、D 4 、D 01 Conduction and transformer T 2 The secondary side homonymous end induces current to pass through D 12 Give electric capacity C 13 Charge and supply capacitor C 12 Discharging, current through diode D 22 To capacitor C 23 Charge and supply capacitor C 22 Discharging, current through diode D 2 To the load R L Supplying power, current flowing through the load via diode D 03 Inflow transformer T 3 The same name end of the secondary side forms a secondary side loop and is connected with a transformer T 3 The primary side current direction is uniform. Second loop, D 14 、D 24 、D 4 、D 01 Conduction and transformer T 4 The secondary side homonymous terminal induces a current to pass through the diode D 14 Give electric capacity C 11 Charge and supply capacitor C 14 Discharging, current through diode D 24 To capacitor C 21 Charging; give electric capacity C 24 Discharging, current simultaneously passing through diode D 4 To the load R L Supplying power, current flowing through the load via diode D 01 Inflow transformer T 1 The same name end of the secondary side forms a secondary side loop and is connected with a transformer T 1 The primary side current direction is uniform. Diode D 1 、D 3 、D 02 、D 04 、D 11 、D 13 、D 21 、D 23 Are all turned off. The working state of the secondary side circuit is continued until the main switch VT 2 、VT 4 The re-turn on will change. Inductance L 2 And inductance L 4 The current continues to be the parasitic capacitance C of the drain and the source of the switch tube VT2 、C VT4 Charged to the voltage value of the clamping capacitor C C2 And C C4 Is set in the above-described voltage range. Since the drain-source parasitic capacitance value is very small, the leakage inductance L K2 、L K4 The process of starting to rise the current until the drain-source parasitic capacitance terminal voltage is the clamping capacitance voltage is short, the influence of the process can be ignored in the circuit performance analysis, and the rising time of the drain inductance current is considered to be consistent with the time when the drain-source parasitic capacitance terminal voltage is clamped by the capacitance.
(4) Drain-source parasitic capacitance C VT2 、C VT4 When the voltage rises to the clamping capacitor voltage, the auxiliary switch VT C2 、VT C4 Is turned on, and most of the inductance L is due to the large clamp capacitance relative to the drain-source parasitic capacitance 2 、L 4 Will flow into the clamping capacitor C C2 、C C4 In the main switching tube VT 2 、VT 4 The drain-source voltage is clamped at the voltage of the clamping capacitor, and from this point on the leakage inductance L K2 、L K4 Clamping capacitor C C2 、C C4 And the secondary side capacitor of the transformer will form a resonant circuit, and the voltage ripple is negligible because the secondary side capacitor is designed to be large enough, so that the resonance is analyzedThe process can be equivalently a constant voltage source. This resonance period is related to the value of the leakage inductance and the clamping capacitance (neglecting the effect of drain-source parasitic capacitance) and must be large enough to ensure reliable operation of the circuit. The resonance process continues until the auxiliary switch VT C2 、VT C4 The drive signal comes in.
(5) Auxiliary switch VT C2 、VT C4 The drive signal comes, because the body diode is already turned on in advance, the auxiliary switch realizes zero-voltage turn-on; leakage inductance L in this state K2 、L K4 The current rises approximately linearly and the process continues until the leakage inductance current rises to the inductance current.
(6) When leakage inductance L K2 、L K4 The current rises to the inductance L 2 、L 4 Current, clamp capacitor C C2 、C C4 The voltage stops rising and begins to discharge to the leakage inductance, the leakage inductance current continues to rise, and the process continues to the auxiliary switch VT C2 、VT C4 Ending at turn-off.
(7) Auxiliary switch VT C2 、VT C4 Is turned off, drain-source parasitic capacitance C VT2 、C VT4 Limiting the rising rate of the auxiliary switch terminal voltage, and effectively reducing VT C2 、VT C4 Is not shown. Then clamping capacitor C C2 、C C4 The resonant circuit is exited, and only the drain-source parasitic capacitance C remains VT2 、C VT4 Independent leakage inductance L K2 、L K4 And (5) discharging. This state continues until the drain-source parasitic capacitance drops to u 0 /(3k)。
(8) Drain-source parasitic capacitance C VT2 、C VT4 The voltage drops to u 0 /(3 k), leakage inductance L K2 、L K4 The terminal voltage is reversed, the drain-to-source parasitic capacitance continues to discharge through the drain inductance when the drain inductance current reaches a maximum value and begins to drop at that time, and the process continues until the drain-to-source parasitic capacitance voltage drops to 0.
(9) Drain-source parasitic capacitance C VT2 、C VT4 The voltage drops to 0, the main open-tube diode is conducted, and the leakage inductance L K2 、L K4 Terminal voltage of-u 0 And (3 k), the leakage inductance current linearly decreases, and the inductance current linearly increases under the excitation of an input power supply. This state continues until the drive signal of the main switch comes.
(10) Main switch V T2 、V T4 The drive signal arrives, and as the main switch body diode is already conducted, the main switch realizes zero-voltage turn-on, and the leakage inductance current continues to drop to the end of the inductance current.
(11) Leakage inductance L K2 、L K4 Current drops to inductance L 2 、L 4 Current, main switch V T2 、V T4 At this point in time, the process continues until the leakage inductance current drops to 0. Diode D controlled by the rate of leakage inductance current drop 12 、D 22 、D 2 、D 03 、D 14 、D 24 、D 4 、D 01 The current drop rate of the diode is effectively controlled, the close zero current turn-off is realized, and the reverse recovery loss of the diode can be restrained. After this time, all diodes are turned off, all main switches are turned on, and the inductor current starts to rise linearly, consistent with state (1).
After that, state (12) to state (21), the main switch V T2 Auxiliary switch V TC1 Switch-on/switch-off state of (2) and main switch V T4 Auxiliary switch V TC3 The switching states of the switches are similar and the description is not repeated.
Simulation parameters: all switching frequencies f=100 kHz, transformer transformation ratio k=1, main switching duty cycle d=0.7, input voltage u in =30v, output voltage u 0 =300V, rated power P 0 =1200w. FIG. 3 shows a main switch VT 1 、VT 2 The driving signal, voltage and current waveforms of the main switch can be seen that the main switch realizes zero-voltage opening. FIG. 4 shows an auxiliary switch VT C1 、VT C2 The auxiliary switch can be seen to realize zero-voltage turn-on. FIG. 5 is a clamp capacitor C C1 、C C2 Voltage waveform and input voltage u in Output voltage u 0 The waveform shows that the voltage of the switching tube is equal to the voltage of the clamping capacitor. FIG. 6 shows inductance L 1 、L 2 、L 3 、L 4 The current waveforms of the four modules are equal, and the four modules automatically equalize current. FIG. 7 shows leakage inductance L of a transformer K1 、L K2 、L K3 、L K4 The adjacent two phases of leakage inductance currents are symmetrical, and the power of the transformer is uniform. FIG. 8 shows a capacitor C 11 、C 12 、C 21 、C 22 Is provided. Fig. 9 shows a diode D 11 、D 12 Voltage, current waveform. FIG. 10 is a diode D 1 、D 2 Voltage, current waveform. It can be seen from fig. 9 and 10 that the diode achieves zero current turn-off without reverse recovery loss.
Claims (1)
1. A modular high boost isolated DC/DC converter having an active clamp circuit, characterized by: comprises a direct current input power supply, m modules and a filter capacitor C 0 A load R L ；
The m modules include:
m power master switches VT 1 、VT 2 ...VT m The power main switch VT 1 、VT 2 ...VT m Corresponding drain-source parasitic capacitance C VT1 、C VT2 ...C VTm ；
m clamping capacitances: c (C) C1 、C C2 、...C Cm ；
m inductances: l (L) 1 、L 2 ...L m ；
m transformation ratios are 1: high-frequency transformer T of k 1 、T 2 ...T m The high-frequency transformer T 1 、T 2 ...T m Corresponding leakage inductance L K1 、L K2 ...L Km ；
nm capacitances: c (C) 11 、C 12 ...C nm ；
m (n+2) diodes: d (D) 1 、D 2 、D 3 ...D m-1 、D m ，D 01 、D 02 、D 03 ...D 0(m-1) 、D 0m ，D 11 、D 12 、D 13 ...D 1(m-1) 、D 1m ，...D (n-1)1 、D (n-1)2 、D (n-1)3 ...D (n-1)(m-1) 、D (n-1)m ，D n1 、D n2 、D n3 ...D n(m-1) 、D nm ；
The connection mode is as follows:
primary side end of module 1: inductance L 1 The other end of (a) is connected with a transformer T 1 Primary side homonymous terminal, first power master switch VT 1 Is connected to the drain of the first power auxiliary switch VT c1 Source of first power auxiliary switch VT c1 The drain electrode of (C) is connected with the clamping capacitor C c1 Is a member of the group;
secondary side end of module 1: transformer T 1 The secondary side homonymous terminal of (C) is connected with the capacitor C 11 One end of diode D 11 Anode and diode D of (c) 01 A cathode of (a); capacitor C 11 Is connected with the other end of the capacitor C 21 And diode D 21 An anode of (a); capacitor C 21 Is connected with the other end of the capacitor C 31 And diode D 31 An anode of (a); … and so on, capacitor C (n-1)1 Is connected with the other end of the capacitor C n1 And diode D (n-1)1 An anode of (a); capacitor C n1 And C at one end of (2) (n-1)1 The node between them is connected with diode D n1 Anode of (C), capacitance C n1 Is connected with the other end of diode D 1 An anode of (a);
primary side end of module 2: inductance L 2 The other end of (a) is connected with a transformer T 2 Primary side homonymous terminal, second power master switch VT 2 Is connected to the drain of the second power auxiliary switch VT c2 Source of a second power auxiliary switch VT c2 The drain electrode of (C) is connected with the clamping capacitor C c2 Is a member of the group;
secondary side end of module 2: transformer T 2 The secondary side homonymous terminal of (C) is connected with the capacitor C 12 One end of diode D 12 Anode and diode D of (c) 02 A cathode of (a); capacitor C 12 Is connected with the other end of the capacitor C 22 And diode D 22 An anode of (a); capacitor C 22 Is connected with the other end of the capacitor C 32 And diode D 32 An anode of (a); … and so on, capacitor C (n-1)2 Is connected with the other end of the capacitor C n2 And diode D (n-1)2 An anode of (a); capacitor C n2 And C at one end of (2) (n-1)2 The node between them is connected with diode D n2 Anode of (C), capacitance C n2 Is connected with the other end of diode D 2 An anode of (a);
and so on to module m:
primary side end of module m: inductance L m The other end of (a) is connected with a transformer T m Primary side homonymous terminal, mth power master switch VT m Drain of (d) and mth power master VT m The mth power master VT m The drain electrode of (C) is connected with the clamping capacitor C cm Is a member of the group;
secondary side end of module 2: transformer T m The secondary side homonymous terminal of (C) is connected with the capacitor C 1m One end of diode D 1m Anode and diode D of (c) 0m A cathode of (a); capacitor C 1m Is connected with the other end of the capacitor C 2m And diode D 2m An anode of (a); capacitor C 2m Is connected with the other end of the capacitor C 3m And diode D 3m An anode of (a); … and so on, capacitor C (n-1)m Is connected with the other end of the capacitor C nm And diode D (n-1)m An anode of (a); capacitor C nm And C at one end of (2) (n-1)m The node between them is connected with diode D nm Anode of (C), capacitance C nm Is connected with the other end of diode D m An anode of (a);
the connection mode among the modules is as follows:
negative electrode of direct current input power supply is grounded, and inductance L of module 1 1 One end is connected with the positive pole of the direct current input power supply, and the first power main switch VT 1 Source electrode is grounded, clamping capacitor C c1 The other end is grounded, the transformer T 1 Primary side heteronymous termination transformer T 2 Primary side synonym terminal and transformer T 1 Secondary side heteronymous termination transformer T 2 A secondary side heteronym terminal; diode D 11 Cathode D 22 Anode, diode D 21 Cathode joint D 32 Anode and so on to diode D n1 Cathode-connected diode D 2 Anode, diode D 1 Cathode load R L And filter capacitor C 0 Diode D 01 Is connected with the load R by the anode L And filter capacitor C 0 Is arranged at the other end of the tube;
inductance L of module 2 2 One end of the second power main switch VT is connected with the positive pole of the direct current input power supply 2 Source electrode is grounded, clamping capacitor C c2 The other end is grounded, the transformer T 2 Primary side heteronymous termination transformer T 3 Primary side synonym terminal and transformer T 2 Secondary side heteronymous termination transformer T 3 A secondary side heteronym terminal; diode D 12 Cathode D 23 Anode, diode D 22 Cathode joint D 33 Anode and so on to diode D n2 Cathode-connected diode D 3 Anode, diode D 2 Cathode load R L And filter capacitor C 0 Diode D 02 Is connected with the load R by the anode L And filter capacitor C 0 Is arranged at the other end of the tube;
and so on to module m:
inductance L of module m m One end is connected with the positive electrode of the power supply, and the mth power main switch VT m Source electrode is grounded, clamping capacitor C cm The other end is grounded, the transformer T m Primary side heteronymous termination transformer T 1 Primary side synonym terminal and transformer T m Secondary side heteronymous termination transformer T 1 A secondary side heteronym terminal; diode D 1m Cathode D 21 Anode, diode D 2m Cathode joint D 31 Anode and so on to diode D nm Cathode-connected diode D 1 Anode, diode D m Cathode load R L And filter capacitor C 0 Diode D 0m Is connected with the load R by the anode L And filter capacitor C 0 Is arranged at the other end of the tube;
the control mode is that an interleaving control strategy is adopted between adjacent power switches; the phase difference of the switch driving phases between every two adjacent phases is 180 degrees, the auxiliary switch of each phase is complementarily conducted with the main switch, and enough dead time is reserved;
when the main switch tube VT 2 、VT 4 Drain-source electrodeParasitic capacitance C VT2 、C VT4 The voltage of (2) rises to u 0 At/(3 k):
leakage inductance L K2 、L K4 The current of (1) starts to rise, diode D 12 、D 22 、D 2 、D 03 、D 14 、D 24 、D 4 、D 01 Achieving near zero current conduction;
in the first loop, diode D 12 、D 22 、D 2 、D 03 、D 14 、D 24 、D 4 、D 01 Conduction and transformer T 2 The secondary side homonymous end induces current to pass through D 12 Give electric capacity C 13 Charge and supply capacitor C 12 Discharging, current through diode D 22 To capacitor C 23 Charge and supply capacitor C 22 Discharging, current through diode D 2 To the load R L Supplying power, current flowing through the load via diode D 03 Inflow transformer T 3 The same name end of the secondary side forms a secondary side loop and is connected with a transformer T 3 The primary side current direction is consistent;
in the second loop, D 14 、D 24 、D 4 、D 01 Conduction and transformer T 4 The secondary side homonymous terminal induces a current to pass through the diode D 14 Give electric capacity C 11 Charge and supply capacitor C 14 Discharging, current through diode D 24 To capacitor C 21 Charging; give electric capacity C 24 Discharging, current simultaneously passing through diode D 4 To the load R L Supplying power, current flowing through the load via diode D 01 Inflow transformer T 1 The same name end of the secondary side forms a secondary side loop and is connected with a transformer T 1 The primary side current direction is consistent; diode D 1 、D 3 、D 02 、D 04 、D 11 、D 13 、D 21 、D 23 All are turned off; the working state of the secondary side circuit is continued until the main switch VT 2 、VT 4 The restart will change;
inductance L 2 And inductance L 4 The current continues to be the parasitic capacitance C of the drain and the source of the switch tube VT2 、C VT4 Charged to the voltage value of the clamping capacitor C C2 And C C4 Is a voltage of (2); leakage inductance L K2 、L K4 The process of starting to rise the current until the drain-source parasitic capacitance terminal voltage is the clamping capacitance voltage is short, and the time of rising the drain inductance current is consistent with the time of clamping the drain-source parasitic capacitance terminal voltage by the capacitance.
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Application publication date: 20181023 Assignee: Nanjing Chixun Electric Technology Co.,Ltd. Assignor: CHINA THREE GORGES University Contract record no.: X2023980049857 Denomination of invention: A Modular High Boost Isolation DC/DC Converter with Source Clamping Circuit Granted publication date: 20231027 License type: Common License Record date: 20231206 |
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