CN101242146A - Secure and efficient low-energy consumption switch power circuit - Google Patents
Secure and efficient low-energy consumption switch power circuit Download PDFInfo
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- CN101242146A CN101242146A CNA2007100028685A CN200710002868A CN101242146A CN 101242146 A CN101242146 A CN 101242146A CN A2007100028685 A CNA2007100028685 A CN A2007100028685A CN 200710002868 A CN200710002868 A CN 200710002868A CN 101242146 A CN101242146 A CN 101242146A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/36—Means for starting or stopping converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
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Abstract
The invention relates to a safe high efficient low power consumption switch power supply circuit, comprising a control circuit for controlling frequency of control switch power supply, comprising a first power switch unit located between an output end and a grounding end of a clamper; a starting control circuit for actuating the first power switch unit when starting; a second switch unit located between the first power switch unit and connecting point and grounding end of the starting control circuit. A gate of the second switch unit has four current sources as actuating current sources, a light load pulse width controller for regulating output pulse width and oscillation frequency; a third power switch unit connected between the output end of the first power switch unit and the output end of the optical coupler saves energy and reduces consumption, which saves output current-limiting circuit in traditional circuit, improves conversion efficiency of the circuit, voltage adaptability of the product and reliability of the product enabling greater safety of the product.
Description
Technical field
What the present invention relates to is a kind of power circuit; what be particularly related to is a kind of safe and efficient low-power consumption switching power circuit and technology; comprise the energy-saving control circuit that adopts the high value starting resistance; underloading concussion FREQUENCY CONTROL and minimum pulse width control; adopt the major loop current-limiting circuit of input voltage control; the output voltage abnormal protection of primary side control, the output constant voltage circuit of employing line loss voltage compensation.
Background technology
Traditional switching power circuit mainly comprises: one first rectification and filter circuit, and be used in voltage commutation that will input and alternating component filtered out, described rectification is connected the first siding ring of transformer with filter circuit.One transformer comprises described first siding ring, a second siding ring and a feedback coil and the coupling of described first siding ring.One clamper is used in and absorbs the high pressure self induction electromotive force that first siding ring produces, and described clamper is between the input of second end of described first siding ring and one first power switch unit.One second rectification is the second siding ring that is connected described transformer with filter circuit, and the pulse wave electric voltage that is used in input is rectified into the definite value dc voltage.And comprise pulsewidth and the frequency that a control circuit is used in control circuit.
Only in the conventional switch power circuit, usually adopt the starting resistance of the little resistance of large volume (high-power), not only volume is bigger for it, has also increased power consumption, has reduced efficient, wastes energy.In traditional self-activated switch power circuit, its operating frequency is restricted at transformer state (having comprised the variation of input voltage and load) and feedback electric capacity; Because the uncertainty of transformer characteristic and state, when zero load, be difficult to make it stably to be operated under the operation mode of knocking off between energy-conservation.Adopt the traditional circuit of elementary current limliting, in input AC voltage difference when (110V/230V), output current (or power) widely different, output current (or power) is big when input AC voltage is high, and safety is that number reduces.Traditional circuit can accomplish that the voltage of output voltage sampling end is constant in the nominal load scope, but added wire rod after, electric current produces voltage drop on wire rod resistance, caused descending by the output voltage behind the wire rod.
Summary of the invention
The objective of the invention is to, solve the problem of above-mentioned explanation, the present invention proposes a kind of safe and efficient low-power consumption switching power circuit, described circuit adopts the energy-saving control circuit of high value starting resistance, described circuit adopts the main starting resistance (greater than 5.1M Ω) that is connected in main line high voltage (dc voltage of input AC voltage behind rectifying and wave-filtering) or switching tube drain electrode (collector electrode), little resistance assistant starting resistance with the ancillary low voltage that is connected in the generation of transformer feedback winding, and make the unloaded steady operation operation mode of between controlling, knocking off during with underloading of circuit by assistant starting resistance, reach energy-saving and cost-reducing purpose.
And described circuit adopts underloading concussion FREQUENCY CONTROL and minimum pulse width control.Circuit of the present invention is when unloaded and underloading (rated power less than 20%), adopt minimum pulse width control and FREQUENCY CONTROL technology, suppressed by freely shaking that transformer and feedback electric capacity produce, and limited minimum pulse width, circuit stably has been operated in knock off between energy-conservation under the operation mode.
On the other hand, circuit of the present invention adopts the major loop current-limiting circuit of input voltage control, circuit of the present invention adopts the method for electric resistance partial pressure to raise and is added to Current limited Control assembly (triode in the major loop current-limiting circuit, controllable silicon, voltage comparator) voltage on, the electric current that makes major loop reduces with the rising of input voltage, it is constant substantially to reach interior (AC85--264V or the DC 120--370V) power output (or electric current) of wide-voltage range, saved the output current-limiting circuit in the traditional circuit, improved the conversion efficiency of circuit, improved the voltage adaptation ability of product, improved reliability of products, made product safer.
The present invention proposes the output voltage abnormal protection of primary side control.Circuit of the present invention utilizes an electronic switching circuit; control the electric current of major loop by the change in voltage on the photoelectric coupled device; when output voltage unusual (overload or short circuit are hanged down in set point output voltage); electronic switching circuit starts diminishes the electric current of major loop; thereby reduce power output (or electric current), play effective protective effect.
The present invention adopts the output constant voltage circuit of line loss voltage compensation.Improve the voltage of output voltage sampling end with the increase of output current, come the voltage drop of offset current on wire rod, thereby reach by the constant effect in the nominal load scope of the output voltage behind the wire rod.
For achieving the above object, the technical solution used in the present invention is, proposes a kind of safe and efficient low-power consumption switching power circuit, and it comprises:
One first rectification and filter circuit (RF1), its be used in will input alternating current be rectified into the direct current of string wave mode formula in the mode of full-wave rectification and noise filtering fallen, it connects described rectification and filter circuit RF1 with the first siding ring that is connected transformer (N1);
A described transformer comprises described first siding ring (N1), and a second siding ring N3 is coupled to described first siding ring N1, with a feedback coil N2 and described first siding ring N1 coupling; One clamper CL, it removes galvanic ring or surging obtaining a galvanic current, and described clamper is arranged between the input K1 of second end of described first siding ring N1 and the first power switch unit Q1; One second rectification is the second siding ring N3 that is connected described transformer with filter circuit (RF2), and the pulse wave direct current of importing is rectified into the definite value direct current;
One control circuit is used for the galvanic frequency of pulse wave of control output end; Described control circuit comprises: the described first power switch unit Q1, and it is arranged between the output and earth terminal PGND of described clamper; And the resistance R 1 of between described first power switch unit Q1 and earth terminal, contacting;
One start-up control circuit A is positioned at described clamper CL, between the second end N1B of described feedback coil N3 and the gate G of the described first power switch unit Q1, with being to activate the described first power switch unit Q1 when just starting;
One second switch unit Q2 is between the tie point and described earth terminal PGND of described first power switch unit Q1 and described start-up control circuit A.The gate of described second switch unit Q2 has four current sources as the actuating current source, is respectively; One first Control current source is first end from described feedback coil; One second Control current source is second end from a underloading pulse width controller LL, and one the 3rd current source is from an optical coupler U1, and one the 4th current source is via the output K2 intercepting electric current of resistance R 2 from the described first power switch unit Q1; Described underloading pulse width controller LL is between second end of the second end N1B of described first siding ring N1 and described optical coupler U1, described underloading pulse width controller LL is used to adjust the frequency of oscillation of the wide ripple of output, and the wavelength that prolongs the output pulse wave makes the frequency of described first power switch unit reduce and saves power supply; And
One is connected the output K2 of the described first power switch unit Q1 and the 3rd switch element Q3 between the described optical coupler U1 output, and wherein said the 3rd switch element Q3 is connected the output K2 of the described first power switch unit Q1 with resistance R 3 via resistance R 1;
One is positioned at the pressurizer RE of output of first end of described second siding ring, wherein uses the voltage of a resistance R 7 with the output winding of adjusting second siding ring.
Description of drawings
Fig. 1 shows structure calcspar of the present invention;
Fig. 2 shows component architecture figure of the present invention;
Fig. 3 shows another component architecture figure of the present invention.
Description of reference numerals: C1, C2, C3, C4-electric capacity; The CL-clamper; D1, D2-diode; RF1-first rectification and filter circuit; RF2-second rectification and filter circuit; The N1-first siding ring; N2-one feedback coil; The N3-second siding ring; Q1-first power switch unit; Q2-second switch unit; Q3-the 3rd switch element; LL-underloading pulse width controller; The K1-input; The K2-output; The R11-pressurizer; R1, R2, R3, R4, R5, R6, R7, R8, R9, R11, R12, R17-resistance; The G-gate; The CP-OP comparator; The T-BJT transistor; The U1-coupler; The U2-voltage control device; Vf1-voltage.
Embodiment
Now sincerely form with regard to the structure of this case, with the effect and the advantage that can produce, cooperate graphicly, the mode of operation of preferred embodiment detailed description the inventive method of act this case is as follows.
Power switch unit among the present invention is one or three polar bodys, as is CMOS transistor or BJT transistor (bipolar junction transistor).With the switch of a gate control circuit, when the voltage of gate will start described power switch during the position surely to certain, the maximum current that flows through power switch by the transformer first siding ring becomes the ratio of negative correlation with input voltage then.
Now illustrate that hereinafter low power switch power circuit of the present invention is as follows, and please refer to the structure calcspar of Fig. 1.
One first rectification and filter circuit RF1 are used in the voltage commutation of input and with alternating component and filter out, and described rectification is connected the first siding ring N1 of transformer with filter circuit RF1.One transformer comprises described first siding ring N1, a second siding ring N3 and a feedback coil N2 and described first siding ring N1 coupling.One clamper CL is used in and absorbs the high pressure self induction electromotive force that first siding ring produces, and described clamper CL is between the input K1 of described first siding ring N1A end and the described first power switch unit Q1.One second rectification is the second siding ring N3 that is connected described transformer with filter circuit RF2, and the pulse wave electric voltage that is used in input is rectified into the definite value dc voltage.
One control circuit is used in the pulsewidth and the frequency of control circuit; Described control circuit comprises: one first power switch unit Q1 is between the output and earth terminal PGND of described clamper CL, and the resistance R 1 of contacting between described first power switch unit Q1 and earth terminal.
One start-up control circuit A is positioned at described transformer first siding ring N1A or N1B, between the second end N1B of described feedback coil N3 and the gate G of the described first power switch unit Q1 with being to activate the described first power switch unit Q1 when just starting; Described start-up control circuit A receives the electric current from described transformer first siding ring N1A or N1B, with electric current from the second end N1B of described feedback coil N3, so the gate G that can provide enough electric currents to give the described first power switch unit Q1, when just starting or restarting, to activate the described first power switch unit Q1; One second switch unit Q2 is between the tie point and described earth terminal PGND of described first power switch unit Q1 and described start-up control circuit A.The gate of described second switch unit Q2 has four current sources with as the actuating current source, and be respectively: one first Control current source is first end from described feedback coil; One second Control current source is second end from a underloading pulse width controller LL, and one the 3rd current source is from an optical coupler U1, one the 4th current source, and resistance R 2 is from the output K2 intercepting electric current of the described first power switch unit Q1; Described underloading pulse width controller LL is between second end of the second end N1B of described first siding ring N1 and described optical coupler U1.Described underloading pulse width controller LL is used in the frequency of oscillation of adjusting the wide ripple of output, and the pulse duration that therefore can prolong the output pulse wave makes the frequency of described first power switch unit reduce therefore can save power supply.
One is connected the output K2 of the described first power switch unit Q1 and the 3rd switch element between the described optical coupler U1 output, and wherein said the 3rd switch element Q3 is connected the output K2 of the described first power switch unit Q1 with R3 via resistance R 2; When output voltage unusual (overload or short circuit are hanged down in set point output voltage), described the 3rd switch element Q3 starts diminishes the electric current of major loop, one is positioned at the pressurizer RE of output of first end of described second siding ring, wherein uses the output voltage compensation of a resistance R 7 with the control secondary side.
As shown in Figure 2, the 3rd switch element Q3 among the present invention comprises an electronic switch Q3 and resistance R 11 and R12.Resistance R 11 connects optical coupler U1 second end; Resistance R 12 connects earth terminal PGND.The control end of electronic switch is positioned on the tie point of described resistance R 11 and R12;
Described start-up control circuit A comprises a resistance R 5A and a resistance R 6, described resistance R 5A is between the gate G of the second end N1B of described first siding ring N1 and the described first power switch assembly Q1, and described resistance R 6A is between the input of the second end N2B of described feedback coil N2 and the described first power switch assembly; Described underloading pulse width controller comprises the capacitor C 1 and a resistance R 9 of a resistance R 8A and a capacitor C 2.
Described pressurizer RE comprises an OP comparator C P and a BJT transistor T.The reference edge of comparator is second end, and input is the 3rd end.Output is first end, when the voltage height of the 3rd end during at second end then output can output signal to activate described transistor T.
The input of described optical coupler be an optical diode its be coupled to output.One resistance R 7 is connected between the input and earth terminal of optical coupler.
One resistance R 6 is connected between the 3rd end of the high-voltage output end of second rectification and filter circuit RF2 and OP comparator C P.One resistance R 5 is connected between the output of the 3rd end of OP comparator and pressurizer RE.The function of R5 and R6 is to be used in the usefulness of doing dividing potential drop.One resistance R 4 is connected between the input of the voltage output end of second rectification and filter circuit RF2 and optical coupler U1.
Resistance R 1 is connected between the output K2 and earth terminal PGND of the first power switch unit Q1, and resistance R 2 is connected between the output K2 of the gate G of second switch unit Q2 and the first power switch unit Q1.Resistance R 3 is connected between the input K1 of the input K1 of second switch unit Q2 and the 3rd switch element Q3.Capacitor C 4 is connected between the second end N2B and earth terminal PGND of feedback coil N2.Rectifier D2 is connected between the input N2A and earth terminal PGND of feedback coil N2.
One resistance R 5A is connected between the gate G of the second end N1B of described first siding ring N1 and the described first power switch unit Q1.Resistance R 6 is connected between the second end N2B of the gate G of the described first power switch unit Q1 and described feedback coil N2.One resistance R 7 and a capacitor C 3 are connected between the first end N2B of the gate G of the first power switch unit Q1 and described feedback coil N2.One resistance R 8 and a capacitor C 2 are connected between the first end N1A of the gate G of second switch unit Q2 and described feedback coil N2.One resistance R 9 and a capacitor C 1 are serially connected between the output of the gate G of described second switch unit Q2 and described optical coupler U1.One resistance R 2 and a resistance R 3 are serially connected between the input of the output K2 of the first power switch unit Q1 and described the 3rd switch element.Resistance R 4 is serially connected between the contact of second switch unit and resistance R 2 and R3, and diode D1 is serially connected between the contact of the second end N1B of first siding ring N1 and described capacitor C 1 and described resistance R 9.
Resistance R 5B is between the first end N1A and the second end N1B of described first siding ring N1.Or as shown in Figure 3, do not connect resistance R 5B, and another resistance R 8B is connected between the gate G of the first end N1A of described first siding ring N1 and described second switch unit Q2.
The first power switch unit Q1 described in the present invention, described second switch unit Q2, described the 3rd switch element Q3 are CMOS (complementary-symmetric metal oxide semiconductor) transistor (or saying the field-effect transistor into CMOS accurately) or BJT transistor (bipolarjunction transistor).
Operation principle of the present invention is described:
(1) starts
The DC main line high voltage " HV+ " (the N1A pin of transformer T1) of input AC voltage behind rectifying and wave-filtering is added on the K1 utmost point and main starting resistance R5A (greater than 5.1M Ω) of power switch pipe Q1 through the elementary winding N1 of transformer T1; And give the charging of G polar net network by R5A, Q1-G voltage is during greater than its thresholding, Q1 produces electric current, and the strong positive feedback by T1 (C4 → feedback winding N2 → C3 → R7) makes its saturation conduction; When major loop (electric current of primary winding N1 → Q1 → R1) at the voltage that produces on the R1 greatly to can make the Q2 conducting time, the Q1-G network voltage is released, Q1 ends, reverse voltage (the N2A-that N2 senses, N2B+) charge to C3 by R6, R7, and charge to C4 by D2, set up boost voltage, the voltage sensed of secondary winding N3 is exported after by second rectifying and wave-filtering simultaneously.When boost voltage set up after, then (the acting in conjunction generation starting resistor of N2 → R7 → C3) made the circuit operate as normal by R5A and R6 and feedback branch road when circuit was restarted.R5B is the another kind of connection of main starting resistance.
(2) frequency and minimum pulse width control
After the operate as normal of circuit is set up, when unloaded and underloading, the voltage Vf1 that photoelectrical coupler U1 produces is higher, and (Vf1 → R9 → C1 → Q2-G) charges to the value of Vf1 to give C1 by R9, as Q1 once more during saturation conduction, (Q2-G → C1 → D1 → Q1), the discharging current of C1 forces to drag down the voltage of Q2-G to C1 by the D1 discharge, finish until discharge, determined the minimum pulse width of Q1 conducting this discharge time.When Q1 by the time, Vf1 charges to C1 by R9 once more, its charging current has been raised the voltage of Q2-G, makes Q2 can continue conducting, transformer and the feedback electric capacity generation of having released freely shake voltage.This circuit has suppressed by freely shaking that transformer and feedback electric capacity produce, and has limited minimum pulse width, circuit stably is operated in knock off between energy-conservation under the operation mode.When heavy duty, the voltage of Vf1 is lower, and as Vf1 during less than the tube voltage drop of D1+Q1, circuit recovers freely shaking by transformer and the control of feedback electric capacity.
(3) voltage-controlled current limliting
When the Q1 saturation conduction, main line high voltage HV+ is added on the primary winding N1, and the transformer mutual inductance makes N2 produce (N2A+, voltage V1 N2B-), V1 on the numerical value: HV+=N2: N1.V1 produces electric current I f1 (C2 only makes every straight of) on R8A, If1=(HV+ * N2 ÷ N1) ÷ R8A, and promptly the high more If1 of HV+ is big more, and the voltage that If1 produces on R4 also can be high more; And during Q2 conducting voltage constant (temperature is certain), the voltage that main circuit current produces on R1 (R2, R3 dividing point) will be confined low more, and main circuit current also will be more little.Cooperate transformer to adjust R4 and R8A, can reach the constant substantially characteristic of (at AC85--264V or DC120--370V) power output in the wide-voltage range, electric current was little when just voltage was high.R8B is the another kind of connection of this function.
(4) output voltage abnormal protection
Q3, R3, R11, R12 form an electronic switching circuit in the circuit; the voltage signal Vf1 that photoelectrical coupler U1 produces; secondary output voltage and load state have been reflected; when output voltage just often the voltage of Vf1 on R11, R12 dividing point greater than the conducting voltage of Q3; Q3 conducting R2, R3 dividing potential drop produce main circuit current on R1 voltage raises; when output voltage unusual (overload or short circuit are hanged down in set point output voltage); Q3 loses the dividing potential drop effect by R3; the electric current of R1 of flowing through is dragged down; thereby reduce power output (or electric current), play a protective role.
(5) line loss voltage compensation
When we are used as the reference zero position to SGND, the voltage drop of output current on R17 produces negative voltage V-at second rectifying and wave-filtering output OUT-, V-is numerically equal to the product of output current and R17, the earth terminal of voltage control device U2 (U2-2) meets reference zero position SGND, voltage sample pull down resistor R16 is connected on V-, when output current increases, it is big that the negative voltage of V-numerically becomes, for the voltage that makes U2 Voltage Reference end (U2-3) remains unchanged, circuit must improve output voltage, comes the voltage drop V-of offset current output current on R17.Cooperate wire rod to adjust R17, can compensate the voltage drop of output current on wire rod, thereby reach by the constant effect in the nominal load scope of the output voltage behind the wire rod.
In sum, the design of consideration of this case hommization, quite realistic demand.Its concrete improvement has disappearance now, compares in prior art obviously to have breakthrough progressive advantage, and the enhancement that has effect really, and non-being easy to reached.This case open or disclose at home with external document and market on, met patent statute.
Above-listed detailed description is specifying at a possible embodiments of the present invention, only described embodiment is not in order to limit claim of the present invention, allly do not break away from the equivalence that skill spirit of the present invention does and implement or change, all should be included in the claim of this case.
Claims (14)
1. low power switch power circuit, it is characterized in that: it comprises:
One first rectification and filter circuit (RF1), its be used in will input alternating current be rectified into the direct current of string wave mode formula in the mode of full-wave rectification and noise filtering fallen, it connects described rectification and filter circuit (RF1) with the first siding ring that is connected transformer (N1);
A described transformer comprises described first siding ring (N1), and a second siding ring (N3) is coupled to described first siding ring (N1), with a feedback coil (N2) and described first siding ring (N1) coupling; One clamper (CL), it removes galvanic ring or surging obtaining a galvanic current, and described clamper is arranged between the input (K1) of second end of described first siding ring (N1) and first power switch unit (Q1); One second rectification is the second siding ring (N3) that is connected described transformer with filter circuit (RF2), and the pulse wave direct current of importing is rectified into the definite value direct current;
One control circuit is used for the galvanic frequency of pulse wave of control output end; Described control circuit comprises: described first power switch unit (Q1), and it is arranged between the output and earth terminal (PGND) of described clamper; And the resistance (R1) of between described first power switch unit (Q1) and earth terminal, contacting;
One start-up control circuit (A) is positioned at described clamper (CL), between second end (N1B) of described feedback coil (N3) and the gate (G) of described first power switch unit (Q1), with being to activate described first power switch unit (Q1) when just starting;
One second switch unit (Q2) is to be positioned between the tie point and described earth terminal (PGND) of described first power switch unit (Q1) and described start-up control circuit A.The gate of described second switch unit (Q2) has four current sources as the actuating current source, is respectively; One first Control current source is first end from described feedback coil; One second Control current source is second end from a underloading pulse width controller (LL), one the 3rd current source is from an optical coupler (U1), and one the 4th current source is via output (K2) the intercepting electric current of resistance (R2) from described first power switch unit (Q1); Described underloading pulse width controller (LL) is positioned between second end of second end (N1B) of described first siding ring (N1) and described optical coupler (U1), and described underloading pulse width controller (LL) is used to adjust the frequency of oscillation of the wide ripple of output; And
One is connected the output (K2) of described first power switch unit (Q1) and the 3rd switch element (Q3) between described optical coupler (U1) output, and wherein said the 3rd switch element (Q3) is connected the output (K2) of described first power switch unit (Q1) with resistance (R3) via resistance (R1);
One is positioned at the pressurizer (RE) of output of first end of described second siding ring, wherein uses the voltage of a resistance (R7) with the output winding of adjusting second siding ring.
2. low power switch power circuit according to claim 1 is characterized in that: described the 3rd switch element comprise an electronic switch (Q3) and resistance (R11) with (R12); Described resistance (R11) connects optical coupler (U1) second end; Resistance (R12) connects earth terminal (PGND); The control end of described electronic switch is positioned on described resistance (R11) and the tie point (R12).
3. low power switch power circuit according to claim 1, it is characterized in that: described start-up control circuit (A) comprises resistance (R5A) and a resistance (R6A), described resistance (R5A) is to be positioned between the gate (G) of second end (N1B) of described first siding ring (N1) and the described first power switch assembly (Q1), and described resistance (R6A) is to be positioned between the input of second end (N2B) of described feedback coil (N2) and the described first power switch assembly;
4. low power switch power circuit according to claim 1 is characterized in that: described underloading pulse width controller comprises the electric capacity (C1) and a resistance (R9) of a resistance (R8A), an electric capacity (C2).
5. low power switch power circuit according to claim 1 is characterized in that: described pressurizer (RE) comprises an OP comparator (CP) and a BJT transistor; The reference edge of described comparator is second end, and input is the 3rd end, and output is first end, and described output links to each other with described transistor (T).
6. low power switch power circuit according to claim 1 is characterized in that: the input of described optical coupler be an optical diode its be coupled to output.
7. low power switch power circuit according to claim 1 is characterized in that: described resistance (R7) is connected between the input and earth terminal of optical coupler.
8. low power switch power circuit according to claim 1 is characterized in that: also comprise: a resistance (R6) is connected between the 3rd end of the high-voltage output end of second rectification and filter circuit (RF2) and OP comparator (CP); One resistance (R5) is connected between the output of the 3rd end of OP comparator and pressurizer (RE); One resistance (R4) is connected between the input of the high-voltage output end of second rectification and filter circuit (RF2) and optical coupler (U1).
9. low power switch power circuit according to claim 1, it is characterized in that: described resistance (R1) is connected between the output (K2) and earth terminal (PGND) of described first power switch unit (Q1), and described resistance (R2) is connected between the output (K2) of the gate (G) of second switch unit (Q2) and first power switch unit (Q1); Described resistance (R3) is connected between the input (K1) of the input (K1) of second switch unit (Q2) and the 3rd switch element (Q3), described electric capacity (C4) is connected between second end (N2B) and earth terminal (PGND) of feedback coil (N2), and rectifier (D2) is connected between the input (N2A) and earth terminal (PGND) of feedback coil (N2).
10. low power switch power circuit according to claim 1 is characterized in that: also comprise between first end (N2B) that resistance (R7) and an electric capacity (C3) is connected in the gate (G) of first power switch unit (Q1) and described feedback coil (N2); One resistance (R8) and an electric capacity (C2) are connected between first end (N1A) of the gate (G) of second switch unit (Q2) and described feedback coil (N2); One resistance (R9) and an electric capacity (C1) are serially connected between the output of the gate (G) of described second switch unit (Q2) and described optical coupler (U1); One resistance (R2) and a resistance (R3) are serially connected between the input of the output (K2) of first power switch unit (Q1) and described the 3rd switch element; Resistance (R4) is serially connected between the contact of second switch unit and resistance (R2) and resistance (R3), and diode (D1) is serially connected between the contact of second end (N1B) of first siding ring (N1) and described electric capacity (C1) and described resistance (R9).
11. low power switch power circuit according to claim 1 is characterized in that: also comprise between first end (N1A) and second end (N1B) that a resistance (R5B) is positioned at described first siding ring (N1).
12. low power switch power circuit according to claim 1 is characterized in that: also comprise between the gate (G) that a resistance (R8B) is positioned at first end (N1A) of described first siding ring (N1) and described second switch unit (Q2).
13. low power switch power circuit according to claim 1 is characterized in that: described first power switch unit (Q1), described second switch unit (Q2), described the 3rd switch element (Q3) is the CMOS transistor.
14. low power switch power circuit according to claim 1, it is characterized in that: described first power switch unit (Q1), described second switch unit (Q2), described the 3rd switch element (Q3) is the BJT transistor, when being that control end is the transistorized base stage of BJT for the BJT transistor.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNA2007100028685A CN101242146A (en) | 2007-02-08 | 2007-02-08 | Secure and efficient low-energy consumption switch power circuit |
| PCT/CN2007/000670 WO2008098424A1 (en) | 2007-02-08 | 2007-03-02 | A safe switch power supply circuit with high efficiency and low energy consume |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNA2007100028685A CN101242146A (en) | 2007-02-08 | 2007-02-08 | Secure and efficient low-energy consumption switch power circuit |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN101242146A true CN101242146A (en) | 2008-08-13 |
Family
ID=39689619
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNA2007100028685A Pending CN101242146A (en) | 2007-02-08 | 2007-02-08 | Secure and efficient low-energy consumption switch power circuit |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN101242146A (en) |
| WO (1) | WO2008098424A1 (en) |
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| WO2013117034A1 (en) * | 2012-02-07 | 2013-08-15 | 广州金升阳科技有限公司 | Ringing chock converter |
| TWI410772B (en) * | 2009-03-12 | 2013-10-01 | System General Corp | Output voltage control circuit of power converter for light-load power saving |
| CN103715910A (en) * | 2012-10-05 | 2014-04-09 | Nxp股份有限公司 | Switched-mode power supply |
| US9660539B2 (en) | 2015-01-30 | 2017-05-23 | 02Micro Inc. | Switching power supplies, and switch controllers for switching power supplies |
| CN108933520A (en) * | 2018-07-19 | 2018-12-04 | 启攀微电子（上海）有限公司 | A kind of super low-power consumption DCDC Switching Power Supply |
| CN113098255A (en) * | 2021-05-20 | 2021-07-09 | 浙江万松电气有限公司 | High-working-voltage and low-power switching power supply circuit |
| CN114157151A (en) * | 2021-11-05 | 2022-03-08 | 苏州美思迪赛半导体技术有限公司 | Digital feedback constant current output control circuit of switching power supply |
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| CN103023337B (en) * | 2013-01-11 | 2015-07-22 | 聚辰半导体(上海)有限公司 | Power circuit of switching power converter |
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Family Cites Families (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2000023461A (en) * | 1998-07-02 | 2000-01-21 | Hitachi Ltd | Power supply circuit |
| JP2002345235A (en) * | 2001-05-11 | 2002-11-29 | Matsushita Electric Ind Co Ltd | Switching power supply |
| JP3548889B2 (en) * | 2001-06-07 | 2004-07-28 | 株式会社村田製作所 | Switching power supply device and electronic device using the same |
| JP4680453B2 (en) * | 2001-09-21 | 2011-05-11 | パナソニック電工制御テクノ株式会社 | Switching power supply |
| JP2003111397A (en) * | 2001-10-02 | 2003-04-11 | Sharp Corp | Switching power unit and method of controlling switching power unit |
| JP3691498B2 (en) * | 2003-06-16 | 2005-09-07 | Ｓｍｋ株式会社 | Self-excited switching power supply circuit |
| US6898093B2 (en) * | 2003-06-24 | 2005-05-24 | Toshiba International Corporation | Power conversion circuit with clamp and soft start |
-
2007
- 2007-02-08 CN CNA2007100028685A patent/CN101242146A/en active Pending
- 2007-03-02 WO PCT/CN2007/000670 patent/WO2008098424A1/en active Application Filing
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| Publication number | Priority date | Publication date | Assignee | Title |
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| TWI410772B (en) * | 2009-03-12 | 2013-10-01 | System General Corp | Output voltage control circuit of power converter for light-load power saving |
| WO2013117034A1 (en) * | 2012-02-07 | 2013-08-15 | 广州金升阳科技有限公司 | Ringing chock converter |
| CN103715910A (en) * | 2012-10-05 | 2014-04-09 | Nxp股份有限公司 | Switched-mode power supply |
| US9219419B2 (en) | 2012-10-05 | 2015-12-22 | Nxp B.V. | Switched mode power supplies |
| CN103715910B (en) * | 2012-10-05 | 2016-11-23 | Nxp股份有限公司 | Switch-mode circuitries |
| US9660539B2 (en) | 2015-01-30 | 2017-05-23 | 02Micro Inc. | Switching power supplies, and switch controllers for switching power supplies |
| TWI589106B (en) * | 2015-01-30 | 2017-06-21 | 凹凸科技國際股份有限公司 | Switching power supplies and switch controllers |
| CN108933520A (en) * | 2018-07-19 | 2018-12-04 | 启攀微电子（上海）有限公司 | A kind of super low-power consumption DCDC Switching Power Supply |
| CN113098255A (en) * | 2021-05-20 | 2021-07-09 | 浙江万松电气有限公司 | High-working-voltage and low-power switching power supply circuit |
| CN114157151A (en) * | 2021-11-05 | 2022-03-08 | 苏州美思迪赛半导体技术有限公司 | Digital feedback constant current output control circuit of switching power supply |
Also Published As
| Publication number | Publication date |
|---|---|
| WO2008098424A1 (en) | 2008-08-21 |
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Open date: 20080813 |