US5646575A - Composite precision, high-frequency rail-to-rail amplifier - Google Patents

Composite precision, high-frequency rail-to-rail amplifier Download PDF

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US5646575A
US5646575A US08/528,636 US52863695A US5646575A US 5646575 A US5646575 A US 5646575A US 52863695 A US52863695 A US 52863695A US 5646575 A US5646575 A US 5646575A
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amplifier
frequency
composite
transconductance
precision
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Don Roy Sauer
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National Semiconductor Corp
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/45—Differential amplifiers
    • H03F3/45071—Differential amplifiers with semiconductor devices only
    • H03F3/45076—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier
    • H03F3/45475—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier using IC blocks as the active amplifying circuit
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/08—Modifications of amplifiers to reduce detrimental influences of internal impedances of amplifying elements
    • H03F1/083—Modifications of amplifiers to reduce detrimental influences of internal impedances of amplifying elements in transistor amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45138—Two or more differential amplifiers in IC-block form are combined, e.g. measuring amplifiers

Definitions

  • This invention relates to operational amplifiers and in particular to an operational amplifier which combines good precision and high-frequency characteristics with a rail-to-rail output.
  • Amplifiers generally fall into different categories, depending on their performance characteristics.
  • One such category includes high-frequency amplifiers, which are characterized by a wide bandwidth and a low open-loop gain.
  • Another such category includes precision amplifiers, which are characterized by a narrower bandwidth but a higher open-loop gain, the latter feature making them more precise, i.e., the voltage drop across the inputs is very small when the amplifier is connected in a closed-loop configuration.
  • a high-frequency amplifier and a precision amplifier are interconnected.
  • the inputs of the precision amplifier are connected across the inputs of the high-frequency amplifier.
  • the output of the precision amplifier is connected to an offset trim port of the high-frequency amplifier.
  • the precision amplifier has relatively little effect, and the output of the composite amplifier is therefore dominated by the high-frequency amplifier.
  • the precision amplifier contributes gain over and above the high-frequency amplifier, and the input offset is dominated by the offset of the precision amplifier.
  • the frequency response curve of the composite amplifier has a single pole and no zeros. This desirable curve is achieved by fabricating the high-frequency and precision amplifiers on a single chip and by arranging the parameters of the circuitry such that the pole of the high-frequency amplifier matches (i.e., cancels) the zero of the precision amplifier under all conditions of time, temperature, process, etc. Thus the pole of the composite amplifier is determined by the pole of the precision amplifier.
  • FIG. 1 illustrates a schematic block diagram of a composite amplifier in accordance with this invention.
  • FIG. 2 illustrates an equivalent circuit for the composite amplifier.
  • FIG. 3 illustrates a graph showing the frequency response curves of the precision amplifier, the high-frequency amplifier and the composite amplifier, respectively.
  • FIG. 4 illustrates a block diagram of a conventional operational amplifier.
  • FIG. 5 illustrates a block diagram of a conventional operational amplifier having an offset trim port.
  • FIG. 6 illustrates a more detailed block diagram of the high-frequency amplifier which forms a part of the composite amplifier of this invention.
  • FIG. 7 illustrates a frequency response curve of the high-frequency amplifier shown in FIG. 6.
  • FIG. 8 illustrates a more detailed block diagram of the composite amplifier, showing both the high-frequency amplifier and the precision amplifier.
  • FIG. 9 illustrates curves showing the frequency response of the high-frequency and precision amplifiers, respectively.
  • FIG. 1 illustrates a composite amplifier A c in accordance with the invention which includes a precision amplifier A p and a high-frequency amplifier A hf .
  • the inputs of amplifiers A p and A hf are connected in the manner shown to input terminals T 1 and T 2 , which receive a differential input signal V in .
  • the output of precision amplifier A p is connected through a resistor R to an offset trim port T 3 of high-frequency amplifier A hf .
  • a single-ended output signal V out is generated at a terminal T 4 .
  • FIG. 2 illustrates an equivalent circuit which helps to show the operation of composite amplifier A c .
  • Feeding the output of amplifier A p to the offset trim port T 3 is equivalent to inserting a voltage source V s in series with the input of the high-frequency amplifier A hf .
  • V s the voltage source
  • the offset of amplifier A hf is 1 mV and amplifier A p contributes a gain of 99, then the offset at the input terminals of composite amplifier A c will be only 10 ⁇ V.
  • Illustrative frequency response curves for amplifiers A p , A hf and A c are shown in FIG. 3.
  • the frequency response of precision amplifier A p represented by curve 1
  • the frequency response of high-frequency amplifier A hf represented by curve 2
  • the frequency response of the composite amplifier A c is represented by curve 3, which is the product of curves 1 and 2.
  • Curve 3 has a single pole which coincides with the pole of amplifier A p .
  • FIG. 4 illustrates a more detailed block diagram of a conventional operational amplifier. This represents the structure of precision amplifier A p and high-frequency amplifier A hf (less the offset trim port).
  • the amplifier shown in FIG. 4 includes an input stage, a second stage and an output stage. This structure is described in greater detail in numerous sources, including, for example, Thomas M. Frederiksen, "Intuitive IC OP Amps", 1984, pages 12-16, which is incorporated herein by reference.
  • the input stage includes a differential amplifier and a current mirror, which together operate to transform the differential input voltage V in into a single-ended current I out .
  • the combination of the differential amplifier and current mirror are sometimes referred to as a "transconductance amplifier” which has a transfer function I out /V in and which is designated by the reference gm1 in FIG. 4.
  • the second stage includes a compensation capacitor C1.
  • the bandwidth of the amplifier depends on where the current I out has a unity gain into capacitor C1 referenced to V in .
  • the low-frequency pole is normally set by a parasitic resistance, shown as R1, that can be viewed as connected in parallel with capacitor C1. Since the input stage is CMOS, the output of the transconductance amplifier gm1 will be somewhat dependent on process and temperature.
  • the output stage includes a buffer B1 which has a high input impedance and is connected in a unity gain configuration.
  • FIG. 5 illustrates a block diagram of the amplifier A hf including the offset trim port T 3 .
  • a second transconductance amplifier gm2 introduces a current I trim into capacitor C1 (actually, as shown by the arrow, I trim flows out of capacitor C1).
  • the voltage at the trim port T 3 is adjusted such that in the presence of negative feedback, the voltage V in is equal to zero.
  • FIG. 6 illustrates the high-frequency amplifier A hf configured in accordance with the invention.
  • amplifier A hf the capacitor/buffer configuration of FIG. 5 is replaced with a transconductance (gm3)/virtual ground configuration in order to provide a rail-to-rail output stage.
  • the output of transconductance amplifier gm1 now goes to a virtual ground, which means that the output of gm1 effectively sees a short to ground.
  • Transconductance stage gm3 is also a CMOS input stage. This removes any bias current loading at the output of transconductance amplifier gm1.
  • the compensation capacitor C1 is shown in parallel with transconductance amplifier gm3.
  • the resistor R1 in FIGS. 4 and 5 has effectively been replaced by the combination of a network of resistors R2 and R3 and transconductance amplifier gm2. Since the transfer function of a transconductance amplifier is in the form I/V, a transconductance amplifier can be viewed as the equivalent of a resistor have a value equal to the inverse of the transfer function. Therefore, the total resistance in parallel with capacitor C1 is equal to (1/gm2)*(R2+R3)/R2.
  • the transfer function of amplifier A hf is shown in FIG. 7. As is well known, the pole occurs at a frequency equal to 1/2 ⁇ RC. Substituting the value C1 for the compensation capacitor C1 and the value (1/gm2)*(R2+R3)/R2 for R yields the following expression of the pole frequency f pole in terms of C1, gm2, R2 and R3:
  • Amplifier A hf reaches unity gain at a frequency equal to gm1/2 ⁇ C1.
  • FIG. 8 shows amplifiers A hf and A p connected together so as to form a composite amplifier in accordance with the invention.
  • Precision amplifier A p includes a transconductance amplifier gm4 and a compensation capacitor C2.
  • Transconductance amplifier gm4 should be formed in CMOS, and transconductance amplifiers gm1 and gm4 should be formed on the same chip and fabricated such that they essentially track each other regardless of process, temperature, output load, etc.
  • gm2 drops out of the equation, and the pole and zero are found to track each other if the required ratios of resistors (R2, R3, R4), capacitors (C1, C2) and gains (gm1, gm4) are maintained.
  • the transconductance amplifiers gm2 and gm3 need not track each other or gm1 or gm4.
  • the composite amplifier disclosed herein has extremely high open loop gain, extremely high bandwidth and extremely low offset. Because the CMOS transconductance amplifier gm3 is used in place of a conventional buffer in the output stage of the high-frequency amplifier A hf , the composite amplifier operates rail-to-rail.

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  • Power Engineering (AREA)
  • Amplifiers (AREA)

Abstract

A composite amplifier is constructed by connecting the respective input terminals of a high-frequency amplifier and a precision amplifier together and by connecting the output of the precision amplifier to the offset trim port of the high-frequency amplifier. The amplifiers are structured such than a pole in the frequency response curve of the high-frequency amplifier cancels a zero in the frequency response curve of the precision amplifier, thereby producing a single pole roll off response curve for the composite amplifier. In the preferred embodiment the high-frequency and precision amplifiers are formed on a single chip and the pole-zero match is therefore maintained at all conditions of temperature and other variables.

Description

FIELD OF THE INVENTION
This invention relates to operational amplifiers and in particular to an operational amplifier which combines good precision and high-frequency characteristics with a rail-to-rail output.
BACKGROUND OF THE INVENTION
Amplifiers generally fall into different categories, depending on their performance characteristics. One such category includes high-frequency amplifiers, which are characterized by a wide bandwidth and a low open-loop gain. Another such category includes precision amplifiers, which are characterized by a narrower bandwidth but a higher open-loop gain, the latter feature making them more precise, i.e., the voltage drop across the inputs is very small when the amplifier is connected in a closed-loop configuration.
It is difficult to achieve the dual objectives of high-frequency and precise operation in a single amplifier because the very features which broaden the bandwidth of the amplifier also tend to reduce its open-loop gain. Similarly, the design criteria which increase open-loop gain tend to reduce the high-frequency response of the amplifier.
As shown in U.S. Pat. No. 5,045,805, it is known to increase open-loop gain by connecting a pair of high-frequency amplifiers in a cascade arrangement. Since the total gain is then the product of the individual gains, the precision of the amplifier pair is improved. However, such arrangements require a compensation network to maintain stability and adjustable circuitry for proper operation.
SUMMARY OF THE INVENTION
In a composite amplifier according to this invention, a high-frequency amplifier and a precision amplifier are interconnected. The inputs of the precision amplifier are connected across the inputs of the high-frequency amplifier. The output of the precision amplifier is connected to an offset trim port of the high-frequency amplifier. At high frequencies, the precision amplifier has relatively little effect, and the output of the composite amplifier is therefore dominated by the high-frequency amplifier. Conversely, at low frequencies, the precision amplifier contributes gain over and above the high-frequency amplifier, and the input offset is dominated by the offset of the precision amplifier.
The frequency response curve of the composite amplifier has a single pole and no zeros. This desirable curve is achieved by fabricating the high-frequency and precision amplifiers on a single chip and by arranging the parameters of the circuitry such that the pole of the high-frequency amplifier matches (i.e., cancels) the zero of the precision amplifier under all conditions of time, temperature, process, etc. Thus the pole of the composite amplifier is determined by the pole of the precision amplifier.
BRIEF DESCRIPTION OF THE DRAWING
The principles of this invention will be best understood by reference to the following figures of the drawing, in which like elements are identified by similar reference numerals.
FIG. 1 illustrates a schematic block diagram of a composite amplifier in accordance with this invention.
FIG. 2 illustrates an equivalent circuit for the composite amplifier.
FIG. 3 illustrates a graph showing the frequency response curves of the precision amplifier, the high-frequency amplifier and the composite amplifier, respectively.
FIG. 4 illustrates a block diagram of a conventional operational amplifier.
FIG. 5 illustrates a block diagram of a conventional operational amplifier having an offset trim port.
FIG. 6 illustrates a more detailed block diagram of the high-frequency amplifier which forms a part of the composite amplifier of this invention.
FIG. 7 illustrates a frequency response curve of the high-frequency amplifier shown in FIG. 6.
FIG. 8 illustrates a more detailed block diagram of the composite amplifier, showing both the high-frequency amplifier and the precision amplifier.
FIG. 9 illustrates curves showing the frequency response of the high-frequency and precision amplifiers, respectively.
DETAILED DESCRIPTION OF THE INVENTION
FIG. 1 illustrates a composite amplifier Ac in accordance with the invention which includes a precision amplifier Ap and a high-frequency amplifier Ahf. The inputs of amplifiers Ap and Ahf are connected in the manner shown to input terminals T1 and T2, which receive a differential input signal Vin. The output of precision amplifier Ap is connected through a resistor R to an offset trim port T3 of high-frequency amplifier Ahf. A single-ended output signal Vout is generated at a terminal T4.
FIG. 2 illustrates an equivalent circuit which helps to show the operation of composite amplifier Ac. Feeding the output of amplifier Ap to the offset trim port T3 is equivalent to inserting a voltage source Vs in series with the input of the high-frequency amplifier Ahf. At high frequencies, amplifier Ap has very little effect, and the high-frequency amplifier Ahf dominates. At low frequencies, amplifier Ap contributes gain over and above the gain provided by amplifier Ahf. Note that the voltage source Vs is connected in the series path between terminals T1 and T2. Thus, for example, if the offset of amplifier Ahf is 1 mV and amplifier Ap contributes a gain of 99, then the offset at the input terminals of composite amplifier Ac will be only 10 μV.
Illustrative frequency response curves for amplifiers Ap, Ahf and Ac are shown in FIG. 3. As indicated, the frequency response of precision amplifier Ap, represented by curve 1, has a pole at a low frequency and a zero at a frequency fpz which coincides with unity gain of amplifier Ap into the voltage source Vs. The frequency response of high-frequency amplifier Ahf, represented by curve 2, has a single pole which also occurs at frequency fpz. The frequency response of the composite amplifier Ac is represented by curve 3, which is the product of curves 1 and 2. Curve 3 has a single pole which coincides with the pole of amplifier Ap. Because the zero of curve 1 matches the pole of curve 2, cancellation occurs in the corresponding region of curve 3. The frequency response of the composite amplifier (curve 3) therefore exhibits a high gain at low frequencies and, after its single pole is passed, a smooth decrease in gain until unity gain is reached at a frequency substantially higher than fpz.
Obtaining this smooth decrease depends upon insuring that the pole of curve 2 matches the zero of curve 1 under all conditions of temperature, time, etc. How this is accomplished will now be described.
FIG. 4 illustrates a more detailed block diagram of a conventional operational amplifier. This represents the structure of precision amplifier Ap and high-frequency amplifier Ahf (less the offset trim port). The amplifier shown in FIG. 4 includes an input stage, a second stage and an output stage. This structure is described in greater detail in numerous sources, including, for example, Thomas M. Frederiksen, "Intuitive IC OP Amps", 1984, pages 12-16, which is incorporated herein by reference. The input stage includes a differential amplifier and a current mirror, which together operate to transform the differential input voltage Vin into a single-ended current Iout. The combination of the differential amplifier and current mirror are sometimes referred to as a "transconductance amplifier" which has a transfer function Iout /Vin and which is designated by the reference gm1 in FIG. 4.
The second stage includes a compensation capacitor C1. The bandwidth of the amplifier depends on where the current Iout has a unity gain into capacitor C1 referenced to Vin. The low-frequency pole is normally set by a parasitic resistance, shown as R1, that can be viewed as connected in parallel with capacitor C1. Since the input stage is CMOS, the output of the transconductance amplifier gm1 will be somewhat dependent on process and temperature.
The output stage includes a buffer B1 which has a high input impedance and is connected in a unity gain configuration.
A more detailed description of an input stage, a second stage and an output stage is found in application Ser. No. 08/205,530, filed Mar. 3, 1994 (now U.S. Pat. No. 5,414,388), application Ser. No. 08/205,573, filed Mar. 3, 1994, and application Ser. No. 08/148,121, filed Nov. 5, 1993, respectively, each of which is commonly owned by the assignee hereof and is incorporated herein by reference in its entirety.
FIG. 5 illustrates a block diagram of the amplifier Ahf including the offset trim port T3. A second transconductance amplifier gm2 introduces a current Itrim into capacitor C1 (actually, as shown by the arrow, Itrim flows out of capacitor C1). The voltage at the trim port T3 is adjusted such that in the presence of negative feedback, the voltage Vin is equal to zero.
FIG. 6 illustrates the high-frequency amplifier Ahf configured in accordance with the invention. In amplifier Ahf, the capacitor/buffer configuration of FIG. 5 is replaced with a transconductance (gm3)/virtual ground configuration in order to provide a rail-to-rail output stage. The output of transconductance amplifier gm1 now goes to a virtual ground, which means that the output of gm1 effectively sees a short to ground. Transconductance stage gm3 is also a CMOS input stage. This removes any bias current loading at the output of transconductance amplifier gm1. Thus, with this architecture, the open-loop gain of the amplifier is very high even when the output is heavily loaded. The compensation capacitor C1 is shown in parallel with transconductance amplifier gm3.
With the arrangement shown in FIG. 6 the resistor R1 in FIGS. 4 and 5 has effectively been replaced by the combination of a network of resistors R2 and R3 and transconductance amplifier gm2. Since the transfer function of a transconductance amplifier is in the form I/V, a transconductance amplifier can be viewed as the equivalent of a resistor have a value equal to the inverse of the transfer function. Therefore, the total resistance in parallel with capacitor C1 is equal to (1/gm2)*(R2+R3)/R2.
The transfer function of amplifier Ahf is shown in FIG. 7. As is well known, the pole occurs at a frequency equal to 1/2πRC. Substituting the value C1 for the compensation capacitor C1 and the value (1/gm2)*(R2+R3)/R2 for R yields the following expression of the pole frequency fpole in terms of C1, gm2, R2 and R3:
F.sub.pole =gm2*R2/((R2+R3)*2*π*C1)
Amplifier Ahf reaches unity gain at a frequency equal to gm1/2πC1.
FIG. 8 shows amplifiers Ahf and Ap connected together so as to form a composite amplifier in accordance with the invention. Precision amplifier Ap includes a transconductance amplifier gm4 and a compensation capacitor C2. Transconductance amplifier gm4 should be formed in CMOS, and transconductance amplifiers gm1 and gm4 should be formed on the same chip and fabricated such that they essentially track each other regardless of process, temperature, output load, etc.
Referring now to FIG. 9, the zero in the transfer function for amplifier Ap occurs where the gain of gm4 through gm2 equals the gain of gm1. At the zero frequency fzero, the following relationship holds:
gm1=(gm4/(2*π*f.sub.zero *C2))*(R3'/(R4+R3'))*gm2
where R3'=R2*R3/(R2+R3)
Solving for fzero yields the following:
f.sub.zero =(gm4/gm1)*(1/2*π*C2)*(R3'/(R4+R3'))*gm2
As noted above, it is desired to have the pole amplifier Ahf cancel the zero of amplifier Ap. In this situation fpole =fzero =fpz (see FIG. 3).
Equating the above expressions for fpole and fzero yields:
((R2+R3')/R2)*(R4/(R4+R3'))=(gm4/gm1)*(C2/C1)
Thus gm2 drops out of the equation, and the pole and zero are found to track each other if the required ratios of resistors (R2, R3, R4), capacitors (C1, C2) and gains (gm1, gm4) are maintained. In particular, the transconductance amplifiers gm2 and gm3 need not track each other or gm1 or gm4.
The composite amplifier disclosed herein has extremely high open loop gain, extremely high bandwidth and extremely low offset. Because the CMOS transconductance amplifier gm3 is used in place of a conventional buffer in the output stage of the high-frequency amplifier Ahf, the composite amplifier operates rail-to-rail.
While a particular embodiment of this invention has been described, numerous alternative embodiments within the spirit of this invention are possible and will be apparent to person skilled in the art.

Claims (12)

I claim:
1. A composite amplifier comprising a first amplifier and a second amplifier, said second amplifier having an offset trim port, respective inputs of said first and second amplifiers being connected together and an output of said first amplifier being connected to said offset trim port.
2. The composite amplifier of claim 1 wherein a voltage applied to said offset trim port controls a current which is summed with a current supplied by an input stage of said second amplifier.
3. The composite amplifier of claim 1 wherein a pole in a frequency response curve of said second amplifier occurs at substantially the same frequency as a zero in a frequency response curve of said first amplifier.
4. The composite amplifier of claim 1 wherein said second amplifier comprises a first transconductance amplifier having inputs connected to inputs of said second amplifier and a second transconductance amplifier having inputs connected to said offset trim port.
5. The composite amplifier of claim 4 wherein outputs of said first and second transconductance amplifiers are connected together.
6. The composite amplifier of claim 5 wherein said second amplifier further comprises a third transconductance amplifier having an input connected to the outputs of said first and second transconductance amplifiers.
7. The composite amplifier of claim 6 wherein said second amplifier further comprises a capacitor, said capacitor being connected in parallel with said third transconductance amplifier.
8. The composite amplifier of claim 7 wherein said first amplifier comprises a fourth transconductance amplifier.
9. The composite amplifier of claim 8 wherein a gain of said first transconductance amplifier is substantially equal to the product of the respective gains of said second and fourth transconductance amplifiers.
10. The composite amplifier of claim 1 wherein said first amplifier comprises a precision amplifier and said second amplifier comprises a high-frequency amplifier.
11. The composite amplifier of claim 1 wherein an inverting input of said first amplifier is connected to a non-inverting input of said second amplifier.
12. The composite amplifier of claim 1 wherein a non-inverting input of said first amplifier is connected to an inverting input of said second amplifier.
US08/528,636 1995-09-14 1995-09-14 Composite precision, high-frequency rail-to-rail amplifier Expired - Lifetime US5646575A (en)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2000003476A1 (en) * 1998-07-13 2000-01-20 Steensgaard Madsen Jesper Wide-bandwidth operational amplifier
US7777568B2 (en) 2004-12-02 2010-08-17 Mandate Chips and Circuits Pvt. Ltd. High frequency receiver preamplifier with CMOS rail-to-rail capability
US8803557B2 (en) * 2012-12-26 2014-08-12 SK Hynix Inc. Comparator circuit and signal comparison method
US20220244322A1 (en) * 2021-01-29 2022-08-04 Infineon Technologies Ag Apparatuses and methods for electrical current sensing

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3573644A (en) * 1969-03-20 1971-04-06 Hewlett Packard Co Dc stabilized wide band amplifier
US3757241A (en) * 1971-11-24 1973-09-04 Keithley Instruments A c amplifier having d c bias stabilization
US4532479A (en) * 1982-09-09 1985-07-30 Signetics Corporation Differential amplifier circuit with rail-to-rail capability
US5045805A (en) * 1990-06-29 1991-09-03 General Electric Company High precision composite amplifier with improved high speed response
US5345191A (en) * 1992-07-31 1994-09-06 Leader Electronics Corp. Broad-band amplifier
US5414388A (en) * 1994-03-03 1995-05-09 National Semiconductor Corporation Rail to rail operational amplifier input stage

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3573644A (en) * 1969-03-20 1971-04-06 Hewlett Packard Co Dc stabilized wide band amplifier
US3757241A (en) * 1971-11-24 1973-09-04 Keithley Instruments A c amplifier having d c bias stabilization
US4532479A (en) * 1982-09-09 1985-07-30 Signetics Corporation Differential amplifier circuit with rail-to-rail capability
US5045805A (en) * 1990-06-29 1991-09-03 General Electric Company High precision composite amplifier with improved high speed response
US5345191A (en) * 1992-07-31 1994-09-06 Leader Electronics Corp. Broad-band amplifier
US5414388A (en) * 1994-03-03 1995-05-09 National Semiconductor Corporation Rail to rail operational amplifier input stage

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
"IC Preamplifier Challenges Choppers on Drift", National Semiconductor, Application Note 79, Feb. 1993.
IC Preamplifier Challenges Choppers on Drift , National Semiconductor, Application Note 79, Feb. 1993. *

Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2000003476A1 (en) * 1998-07-13 2000-01-20 Steensgaard Madsen Jesper Wide-bandwidth operational amplifier
US6573790B2 (en) 1998-07-13 2003-06-03 Esion Llc Wide-bandwidth operational amplifier
US7777568B2 (en) 2004-12-02 2010-08-17 Mandate Chips and Circuits Pvt. Ltd. High frequency receiver preamplifier with CMOS rail-to-rail capability
US20100301939A1 (en) * 2004-12-02 2010-12-02 Mandate Chips and Circuits Pvt. Ltd High frequency receiver preamplifier
US8063702B2 (en) 2004-12-02 2011-11-22 Intelligent Design Limited High frequency receiver preamplifier with CMOS rail-to-rail capability
US8803557B2 (en) * 2012-12-26 2014-08-12 SK Hynix Inc. Comparator circuit and signal comparison method
US20220244322A1 (en) * 2021-01-29 2022-08-04 Infineon Technologies Ag Apparatuses and methods for electrical current sensing
US11668767B2 (en) * 2021-01-29 2023-06-06 Infineon Technologies Ag Apparatuses and methods for electrical current sensing

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